Title of Invention	A METHOD AND A DEVICE FOR COMPENSATING FOR FREQUENCY DRIFT WITHIN A SLEEP CLOCK SIGNAL
Abstract	The present invention relates to a method for compensating for frequency drift within a sleep clock signal used during a slotted paging mode of operation of a wireless mobile station, said mobile station in periodic communication with a base station providing timing signals, said method comprising the steps of; determining an initial frequency of the sleep clock signal following power-up of the mobile station; determining a fixed frequency drift compensation factor representative of a difference between the initial frequency of the sleep clock signal and a pre-determined nominal frequency estimating a dynamic frequency error compensation factor representative of a difference between the initial frequency and a current frequency of the sleep clock signal and iteratively updating the dynamic frequency error compensation factor during the slotted mode of operation by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew. The present invention also relates to a device for compensating for frequency drift within a sleep clock signal.

Title of Invention

A METHOD AND A DEVICE FOR COMPENSATING FOR FREQUENCY DRIFT WITHIN A SLEEP CLOCK SIGNAL

Abstract

The present invention relates to a method for compensating for frequency drift within a sleep clock signal used during a slotted paging mode of operation of a wireless mobile station, said mobile station in periodic communication with a base station providing timing signals, said method comprising the steps of; determining an initial frequency of the sleep clock signal following power-up of the mobile station; determining a fixed frequency drift compensation factor representative of a difference between the initial frequency of the sleep clock signal and a pre-determined nominal frequency estimating a dynamic frequency error compensation factor representative of a difference between the initial frequency and a current frequency of the sleep clock signal and iteratively updating the dynamic frequency error compensation factor during the slotted mode of operation by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew. The present invention also relates to a device for compensating for frequency drift within a sleep clock signal.

Full Text	The invention generally relates to mobile communication systems and in particular to techniques for compensating for frequency drift in a low frequency clock employed during a sleep period between paging slots within a mobile station of a mobile communications system. Description of the Related Art Certain state of the art wireless communication systems, such as Code Division Multiple Access (CDMA) Systems employ slotted paging to allow mobile stations to conserve battery power. In a slotted paging system, paging signals are transmitted from a base station to particular mobile stations only within assigned paging slots separated by predetermined intervals of time. Accordingly, each individual mobile station may remain within a sleep mode during the period of time between consecutive paging slots without risk of missed paging signals. Whether any particular mobile station may switch from an active-mode to a sleep mode depends, however, upon whether the mobile station is currently engaged in any user activity such as processing in put commands entered by the user or processing a telephonic communication on behalf of the user. Assuming though that the mobile station is not currently engaged in any processing on behalf of the user, the mobile station automatically powers down selected internal components during each period of time between consecutive slots. One example of a slotted paging system is disclosed in U. S. Patent No. 5,392,287, entitled "Apparatus and Method for Reducing Power Consumption in a Mobile Receiver issued February 21, 1995, assigned to the assignee of the present invention and incorporated by reference herein. Thus, within a slotted paging system, a mobile station reduces power consumption by disorienting power from selected internal components during a sleep period between consecutive slots. However, even during the sleep period, the mobile station must reliably track the amount of elapsed time to determine when the next slot occurs to permit receive components of the mobile station to power up in time to receive any paging signals transmitted within the slot. One solution to this problem is to operate a high frequency clock throughout the sleep period and to track the amount of elapsed time using the high frequency clock. This solution allows the sleep period to be very precisely tracked using the high frequency clock. However, considerable power is consumed operating the high frequency clock and optimal power savings therefore are not achieved during the sleep period. Hence, it would be desirable to instead employ an alternate low frequency, low power clock during the sleep period to further reduce power consumption. However, low frequency, low power clock signals typically suffer from considerable frequency drift such that the amount of elapsed time during the sleep period cannot be precisely determined. Frequency drift within a mobile station can be particularly significant as a result of temperature variations within the mobile station either as a result of changes in operation of components of the mobile station or as a result of ambient conditions of the mobile station. For example, during an extended telephone call, components of the mobile station may heat to 87 degrees Celsius. During an extended period of inactivity, the temperature of the components may cool to an ambient temperature of, perhaps, 25 degrees Celsius. Moreover, if the user places the mobile telephone in either a very hot or very cold location, the temperature change may be even more significant. Typical low power, low frequency clock signal generators are significantly affected by even relatively minor temperature changes and are even more strongly affected by such broad changes in temperature. Indeed, the amount of drift in a typical low power, low frequency clock signal is sufficiently great such that if used by itself to calculate the elapsed time, there is significant risk that the mobile station will not be reactivated in time to power up components to detect a paging signal transmitted within a next paging slot. Accordingly, important paging signals maybe missed possibly resulting in missed phone calls and the like. Hence, when using a low-frequency clock signal to track time during a sleep period, the mobile station is typically configured to return to an active mode by activating a high frequency clock signal well in advance of a next expected paging slot to thereby avoid possible timing errors. Thus, for example, if the paging slots occur ever 26. 67 milliseconds, the mobile station may be programmed to activate the high frequency clock and to power up receive components after only, for example, 26 milliseconds of sleep to ensure that the next paging slot is not missed. Hence, optimal power savings are not achieved. One technique that has been proposed for compensating for timing errors inherent in low frequency, low power clock signal generators is to adapt a length of a current sleep period based upon a timing accuracy of a previous sleep period. More specifically, if a previous sleep period was determined to be too long due to timing errors in the low power, low frequency clock generator, the mobile station is programmed to wake up earlier in the current sleep period. To determine whether a sleep period is too long or too short, the mobile station attempts to detect a unique word within a received paging signal, such as a message preamble which signifies the beginning of an assigned slot. If the unique word is not detected, the mobile station concludes that it woke up too late and therefore the sleep duration is decreased for subsequent sleep periods. If the unique word was properly received, the mobile station either woke up on time or wake up too early and the sleep duration is in creased slightly for the subsequent sleep period. One problem with the aforementioned technique is that it assumes that any failure to detect the unique word is a result of a timing error. However, there may be other reasons besides the duration of the sleep period that the unique word was not correctly received and demodulated, such as poor communication channel quality conditions. Moreover, even if failure to detect the unique word was a result of a timing error rather than other communication errors, the system still does not precisely correct for errors in the low power, low frequency clock signal and therefore does not provide for optimal power savings. A significant improvement is provided in U. S. Patent Application Serial No. 09/134,808,entitled "Synclironization of a Low Power Oscillator with a Reference Oscillator in a Wireless Communication Device Utilizing Slotted Paging", filed August 14,1998 and assigned to the assignee of the present invention. In the aforementioned patent application, timing errors are corrected without relying upon the failure to receive portions of transmitted signals. Rather, the system includes a frequency error estimation unit for directly estimating the frequency of the low power, low frequency clock. In one example described in the patent application, the frequency error in the low frequency clock is determined by timing the low frequency clock using a high frequency clock during periods of time when the high frequency clock is active. For example, during each paging slot when the high frequency clock signal of the mobile station is activated, the frequency error in the low frequency clock is calculated based upon the high frequency clock. Additionally, the system operates to synchronize the activation of the high frequency clock very precisely to transitions in the low frequency clock signal to further reduce errors. Although the system of the aforementioned patent application provides a significant improvement over systems which rely on the detection of unique words of signals transmitted to the mobile station, considerable room for improvement remains. To permit the mobile station to respond promptly to any keys that have been pressed by a user during a sleep period, it is often desirable to subdivide the sleep period into a sequence of sub-periods, also referred to herein as "catnaps". After each catnap, selected components of the mobile station are powered up sufficiently to detect whether a key on the keypad has been pressed and, if so, the sleep period is aborted and other components of the mobile station are powered up as needed to respond to the'pressed key. The duration of the catnaps are typically not an integer number of cycles of the low frequency sleep mode clock. Accordingly, considerable truncation errors can occur if the low frequency clock, by itself, is employed to time the catnaps. Hence, it would be desirable to provide a system for timing sleep periods using a low frequency clock in such a manner to eliminate substantial truncation errors and aspects of the invention are directed to this end. Also, because the frequency error is calculated only while the mobile station is in an active-mode, it may not properly detect frequency errors occurring during extended sleep periods during which time the temperature of the low frequency clock signal generator decreases significantly. Accordingly, even with the improved system of the patent application, the high frequency clock signal must be usually be activated somewhat in advance of the next expected paging slot to account for remaining timing errors. Hence, optimal power savings are not achieved. It would be also preferable to provide a system wherein frequency drift is estimated effectively to permit an active mode high frequency clock to be turned on as close as possible to the next paging slot to permit maximum power savings during the sleep period and to permit easy reacquisition of a paging signal and it is to these ends that other aspects of the present invention are also directed. SUMMARY OF THE INVENTION In accordance with a first aspect of the invention, a method is provided for tracking the length of a sleep period within a mobile station using a sleep clock. The method operates to precisely calibrate portions of the sleep period. In accordance with the method, a sleep period is initiated with the sleep period subdivided into a sequence of sub-periods each of known duration but wherein the durations of the sub-periods are not necessarily integer multiples of cycles of the sleep clock. Elapsed time is tracked within each individual sub-period of the sleep period using an integer sleep counter which tracks whole cycles of the sleep clock. Any remaining fractional portions of the cycles of the sleep mode clock not accounted for by the integer sleep counter are tracked using a fractional sleep counter, with the fractional sleep counter accumulating remaining fractional portions of sleep clock cycles from one sub-period to the next. In an exemplary embodiment of the first aspect of the invention, the sub periods of the sleep period are "catnaps". Within each catnap, the integer sleep counter is incremented downwardly on each cycle of the sleep clock. When the integer sleep counter reaches 0, the catnap is deemed to be complete. When the catnap is complete, a keypad of the mobile station is checked to determine whether a key has been pressed and, if so, the sleep period is terminated. Whenever the fractional counter overflows, a current value of the integer sleep counter is increased by a integer overflow portion of the fractional sleep counter such that the integer counter then accounts for the over flow. A current value of the fractional sleep counter is reset to be equal only to the remaining fractional portion, if any, of the previous fractional sleep counter value such that the fractional sleep counter continues to track remaining fractional portions of cycles of the sleep mode clock. In accordance with a second aspect of the invention, a method is provided for compensating for frequency drift within a sleep clock signal used to time sleep periods during a slotted paging mode of operation of a wireless mobile station wherein the wireless mobile station receives signals from a base station having high timing accuracy. The method operates to iteratively adjust an estimate of the frequency drift during a sleep mode to enable effective frequency drift compensation. In accordance with the method, an initial frequency of the sleep clock signal is determined following power-up of the mobile station. A fixed frequency drift compensation factor representative of a difference between the initial frequency of the sleep clock signal and a predetermined nominal frequency (that eliminates truncation error) is then determined for computational convenience. A dynamic frequency error compensation factor representative of a difference between the initial frequency and a current dynamic frequency of the slow clock signal (which may vary due to temperature or aging) is estimated. Then, during the slotted mode of operation, the following steps are iteratively performed. The dynamic frequency error compensation factor is updated by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew. In an exemplary implementation, the sleep period length is converted into the number of sleep clocks using the dynamic frequency as the initial estimate. After each wakeup from a sleep period, the mobile station searches for an incoming signal from the base station. As timing is maintained at the base station with very high accuracy, any error made in the initial estimate of dynamic frequency (arising due to truncation effects or temperature-and aging induced frequency drifts) will show up as a "slew" in the timing of the in coming signal. The quantity "slew" indicates the timing difference or offset that the mobile perceives after wakeup from sleep. Then a new value for the dynamic frequency compensation factor is determined by applying a value representative of the amount of the slew to a loop filter. In a preferred implementation, the mobile station is configured to implement both the improved calibration method and the improved frequency drift estimation method. Apparatus embodiments of the invention are also provided. BRIEF DESCRIPTION OF THE DRAWINGS The features, objects, and advantages of the invention will become more apparent from the detailed description set forth below when taken in conjunction with the drawings in which like reference characters identify correspondingly throughout and wherein: FIG. 1 is a timing diagram illustrating a pair of consecutive sleep periods, each including one or more catnap periods, tracked in accordance with an exemplary method of the invention. FIG. 2 is a flow chart illustrating the exemplary method of the invention. FIG. 3 is a timing diagram illustrating various clock signals utilized by the exemplary method of FIG. 2. FIG. 4 is a vector diagram illustrating certain timing values processed by the method of FIG. 2. FIG. 5 is a block diagram illustrating a feedback loop employed by the exemplary method of the invention to estimate frequency drift. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS Referring to the figures, an exemplary embodiment of the invention will now be described. Initially, a method by which the exemplary embodiment operates to time a sleep period using a sleep-mode clock and to calibrate the end of the sleep period precisely with a next paging slot will be described with reference to FIGS. 1-3. The method operates to precisely calibrate the length of the sleep period despite frequency drift which may occur during the sleep period. Then, a method by which the exemplary embodiment operates to estimate the frequency drift will be described with reference to the remaining figures. FIG. 1 is a timing diagram illustrating a pair of consecutive sleep periods 100 and 102 each subdivided into a set of sub-periods or "catnaps" generally denoted by reference numeral 104. During a period of time between each catnap, the mobile station wakes up only those components necessary to determine whether a key has been pressed on the key pad. In the example of FIG. 1, each sleep period includes only two catnaps. In other implementations a different number of catnaps may be employed. Each sleep period is timed primarily using only a sleep-mode clock having a relatively slow frequency, such as a 32 kilohertz clock. As will be described, a transition-mode clock having a substantially higher frequency than the sleep-mode clock is employed at the beginning and end of the sleep period to help calibrate the length of the sleep period. The length of the sleep period is not necessarily an integer number of cycles of the sleep clock. Likewise, the lengths of individual catnaps are not necessarily integer multiples of the sleep clock. To account for fractional portions of the sleep-mode clock, a fractional counter is employed. Also, the complete set of catnaps within the sleep period does not account for the entire period of time within the sleep period. Rather, an initial period of time Ta occurs prior to the start of the first catnap and a final period of time Tc occurs between the end of the last catnap and the end of the sleep period. The initial period Ta occurs because of the first catnap does not begin until a first edge of the sleep-mode clock is detected and the first edge with may be offset from the start of the sleep period. The final time period Tc is provided to permit the system to precisely calibrate the termination of the sleep period with a next paging slot by taking into account the fractional portions of sleep cycles counted using the fractional counter. Referring now to FIG. 2, the method by which the mobile station deter mines the lengths of various catnaps and determines the amount of time Tc necessary to precisely terminate the end of the sleep period with the next paging slot will now be described. The mobile station initiates the sleep period at step 110. At step 112, the integer counter (I_COUNTER) and the fractional counter (F_COUNT) are both set to 0. Then, at step 114, the first of a series of catnaps is initiated. The first catnap commences with a falling edge following the first detected rising edge of the sleep-mode clock which, as noted above, may be offset from the start time of the sleep period by an initial offset time Ta. At step 116, the mobile station determines the number of cycles of the sleep clock within the current catnap based upon the length of the catnap. The length of the catnap is predetermined and values representative of the length may be stored in appropriate memory registers. Then, at step 118, the integer counter is reset to equal the previous value of the integer counter plus the integer number of cycles in the current catnap. Prior to the first execution of step 118, the integer counter is set to 0. Hence, following step 118, the integer counter is simply set to the number of whole cycles of the sleep clock occurring during the first catnap. At step 120, the fractional counter is set to equal the previous value of the fractional counter plus any fractional remainder of the cycles of the sleep mode clock in the catnap. Again, prior to the first execution of step 120, the fractional counter is initially set to 0 and hence, following step 120, the fractional counter is simply set to the fractional number of cycles remaining in the first catnap not accounted for by the integer number of cycles stored within the integer counter. At step 122, if the current catnap is the first catnap, then the offset time Ta between the start of the sleep period and the start of the first catnap is determined. In the preferred implementation, the duration of the offset time is determined by activating a high frequency transition-mode clock prior to the commencement of the sleep period, then counting the number of cycles in the transition-mode clock occurring between the start of the sleep period and the start of the first catnap. Further details regarding the transition-mode clock are provided in a co-pending U. S. Patent Application entitled "Method and Apparatus for Activating a High Frequency Clock Following a Sleep Mode within a Mobile Station Operating in a Slotted Paging Mode", filed contemporaneously herewith, assigned to the assignee of the present application, and incorporated by reference herein. At step 124, the mobile station then determines whether the current cat nap is the second catnap and if so operates to subtract the initial offset time Ta from the current value of the fractional counter in step 126. Hence, during a second catnap, the mobile station resets the fractional counter to compensate for the initial offset time. Continuing, though, with processing occurring during of the first catnap, execution proceeds directly from step 124 to step 126 wherein the mobile station determines the frequency drift in the first catnap. The manner by which the frequency drift is estimated will be described below. The estimate of the frequency drift includes both an integer portion (I_DR1FT) and a fractional remainder portion (FDRIFT). The integer portion represents the amount of frequency drift occurring within the catnap in whole cycles of the sleep-mode clock. The amount of frequency drift will not likely be precisely equal to an integer number of the sleep mode clock cycles. Any fractional remainder is represented by F_DRIFT. At step 128, the mobile station adds IDRIFT to I COUNT and also adds F_DRIFT to F_COUNT to thereby account for both the integer and fractional portions of the frequency drift. Following step 128, it is possible that the fractional counter will be greater than 1. Such may occur, for example, if the total of the fractional portion of the frequency drift determined at step 126 and the fractional portion of the duration of the catnap determined at step 120 collectively exceed one complete cycle of the sleep mode clock. To ensure that the fractional counter remains between 0 and 1.0, the mobile station determines, at step 130, whether the F_COUNT is greater than 1 and, if so, step 132 is performed wherein the integer counter is incremented by 1 and the fractional counter is decremented bill. Following step 132, execution returns to step 130 wherein the mobile station again determines whether the fractional counter is greater than 1.0 and, if so, step 132 is repeated. In this manner, steps 130 and 132 are repeated in a loop until the fractional counter is reset to a value between 0 and 1.0. On the other hand, following step 128, it is possible that the fractional counter will be less than 0. Such may occur if the frequency drift value is a negative value and is larger in magnitude than the fractional remainder determined at step 120. To ensure that the fractional counter remains between 0 and 1.0, the mobile station determines at step 134 whether F_COUNT is less than 0 and, if so, step 136 is performed wherein the integer counter is decremented by 1 and the fractional counter is incremented by 1. Following step 136, execution returns to step 134 wherein the mobile station determines whether the fractional counter is still negative and, if so, step 136 is repeated. In this manner, steps 134 and 136 are repeated in a loop until the fractional counter is reset to a value between 0 and 1.0. At step 138, the mobile station accounts for any necessary wakeup time (or warm-up interval) required at the end of each catnap to allow the components of the mobile station to power up to detect whether any keys on the keypad have been pressed. Accordingly, at step 138, the mobile station determines the duration of the wakeup period in cycles of the sleep-mode clock then subtracts the wakeup period from the value currently held with an integer counter. The length of the wake up period is predetermined and values representative of the length may be stored in appropriate memory registers. Note that any fractional portion of the wakeup period is not separately accounted for. In other implementations, the wakeup period can be divided into an integer portion and a fractional portion with the fractional portion subtracted from the fractional counter as well. Thus, following step 138, the integer counter contains a value indicating the number of cycles of the sleep-mode clock occurring between the beginning of the current catnap and the beginning of the wakeup period at the end of the catnap, adjusted, for example, to account for the frequency drift. Beginning at step 140, the mobile station times the catnap by subtracting 1 from the value of I_COUNT with each tick of the sleep-mode clock then, at step 142, checking to determine whether I_COUNT has reached 0. Once I__COUNT has reached 0, the point and time wherein components of the mobile station need to wakeup to facilitate any required processing at the end of the catnap has been reached. As step 144, the mobile station then begins waking up those components and, upon completion of the wakeup period, performs any necessary fimctions such as determining whether any of the keys on the key pad have been pressed. If any key has been pressed, or if the mobile station, determines that any other processing is required, then the mobile station wakes up at step 146. Depending upon the implementation, this may involve powering up all remaining components of the mobile station or perhaps powering up only those components required to perform the particular required functions. In any case, the high-frequency clock is activated at step 146 and further sleep mode processing is terminated. If, however, at step 144 the mobile station determines that no keys have been pressed and that no other action is required, then execution proceeds to step 148 wherein the mobile stations determines whether the just completed catnap was the last catnap of the sleep period. If not, then at step 150, the mobile station begins the next catnap causing execution to return to stepll6 wherein the mobile station determines the number of cycles of the sleep clock within the new catnap and proceeds as described above. In this manner, until either a key has been pressed or until the last catnap has been completed, the mobile station executes steps 116-150 in a continuous loop. Note that, although the integer counter I_COUNT will always be equal to 0 at the beginning of each catnap loop (i. e., at step 116) the fractional counter FCOUNT will typically not be equal to 0 at the beginning of any catnap other the first. Rather, the fractional counter will retain whatever previous fractional count was held therein. In this matter, the fractional counter accumulates fractional portions of sleep cycles from one catnap to the next. Eventually the fractional counter will likely overflow, i. e., the fractional counter will at some point be set to a value greater than 1.0. If so, then during a first subsequent execution of step 130, the overflow is accounted for by incrementing ICOUNT by 1 and by decrementing F_COUNT by 1. In this manner, upon the completion of each catnap, the fractional counter will again be equal to some value between 0 and 1.0. Thus, only fractional remainders of sleep cycles are carried from one catnap to the next and all integer portions are accounted for within each individual catnap. In other words, the duration of each catnap is calibrated to be within at least one sleep cycle of the intended catnap length. Eventually, at step 148, the mobile station will detect that the just completed catnap is the last catnap and, if so. execution proceeds to step 152 or in the mobile station begins to account for the remaining period of time Tc necessary to wake up the receive components of the mobile station in time for the next paging slot. In some circumstances, only a single catnap will occur within the sleep period, hence the last catnap is also the first catnap. Such may occur, e. g., when the mobile station is woken up due to a key pad event occurring during the first catnap. Earlier it was noted that during a second catnap, at steps 124 and 126, the fractional counter is reset to account for the initial offset time Ty. However, if there is only a single catnap, stepl26 will not have been executed. Accordingly, the mobile station determines, at step 152 whether the just completed catnap was the only catnap and, if so, step 154 is performed to subtract the initial offset time from the current value of the fractional counter. In either case, execution proceeds to step 126 wherein the mobile station then reactivates the transition mode clock to time the remaining amount of time specified by the fi-actional counter and, when that period has elapsed, the mobile station then wakes up at step 146. Thus, FIG. 2 illustrates a method whereby the mobile station precisely calibrates the length of the overall sleep period to wake up receive components of the mobile station just in time to receive a paging signal, if any, provided within the next paging slot. Hence, the receive componerits remain powered down for the maximum possible duration to thereby gain the maximum amount of power savings during the sleep period. Precise calibration is achieved, in part, using the aforementioned fractional sleep counter which ac cumulates fractional portions of complete cycles of the sleep clock from one catnap to the next to permit those fractional portions to be ultimately ac counted for prior to wakeup of the receive components. In the following, a specific example is described for use within a mobile station configured in accordance with IS-95A standard. According to the IS-95A standard, a CDMA mobile station or "subscriber station" operating in a slotted mode maximizes the standby time by going to sleep, based on a parameter. Slot Cycle Index (SCI). The subscriber station wakes up every (1. 28 * 2) sec to monitor its assigned 80 ms slot to receive pages. For example with SCI = 0, the subscriber station ideally remains awake for 80 ms and sleeps for 1.2 sec. As noted above, the station must wake up a sufficient amount of time ahead of the next slot boundary so as to take care of events such as radio frequency (RF) component warm-up, synthesizer stabilization, clock settling, CDMA pilot search and acquisition, finger reassignment and decoder warm up. As shown in FIG. 3, in each sleep cycle the unit sleeps in catnaps to allow good response time if the user presses a key while it is asleep. The sleep cycle length and catnap length are chosen to be multiples of a pseudorandom number period (also known as PN roll) so that upon wake-up, pilot may easily be found. TPN may be, for example, 26.67 milliseconds. Each catnap is further divided into:(l)"sleep time," when the entire unit is put to sleep and (2) "warm-up time," when the RF and analog units are turned on for warm-up. When the subscriber station is asleep, the system time is approximately maintained by clocking the counters that keep track of sleep duration with a combination of the sleep clock for coarse timing (maximum resolution of 1/60k = 16.7 micro-sec) and the transition mode clock (SLPCHIPX8) for fine timing (resolution of 1/(8*1. 2288e6) = 0.102 micro-sec). An example of the events that constitute a sleep cycle is shown in FIG. 3. Waveform E within the figure marks each event in the sleep cycle as follows: Before tl : When it is time to sleep, the software shuts off all unnecessary clock regimes except for the CDMA demodulator and a decoder clock regime, RXCHIPX8 (Waveform B). A catnap (which is a multiple of 26.67 ms) is split into sleep time and warm-up time and programmed as the duration of the first catnap interval through the SLEEP’INTERVAL and WU_TME registers. Software writes an ASIC SLEEP ARM bit of a SLEEP_CTL register, indicating that subscriber station must go to sleep on the next PN roll (indicated bytl). All along, the sleep clock (Waveform D) runs asynchronous to a high frequency CDMA clock regime CHIPX8, while the SLPCHIPX8 (Wave- form C) is in sync with the RXCH1PX8, having been derived the same source,CHIPX8. At time when a PN roll occurs, the RXCHIPX8 clock regime is disabled putting the subscriber station to sleep. It is this point onwards that it is desirable for the sleep period to be very close to multiples of 26.67 ms using counters SLEEP_INTERVAL and WU TIME running off the sleep clock. To account for the asynchronous sleep clock, a transition-mode counter called CHIPX8_SLEEP_TIME starts counting the SLPCHIPXS's that have elapsed from tl to the next rising edge of the sleep clock. At time t2 : the rising edge of sleep clock occurs at which time the SLPCHIPX8 clock regime is disabled, freezing the CHIPX8__SLEEP_TIME, there by providing an estimate of the time duration (t2-tl) in chips units. At time t3: after half a sleep clock duration, a SLEEP_N signal (Waveform A) goes low on the falling edge of the sleep clock causing the other digital, analog and RF components in the phone to transition to a low power mode. If there are Ng’ chips in a sleep clock cycle, the total time elapsed at this point of time is given by: TA ‘ (t2-tl) +(t3-t2) = {CHIPX8_SLEEP_TME +_Nsc} chips. It may be noted that from this definition, TA will be in the range of slow clock cycles. Subsequent catnaps are adjusted to account for this extra time slept owing to the asynchronous sleep crystal. Also a counter SLEEP_INTERVAL running off the sleep clock starts to counts down. At time t4 : the counter SLEEP INTERVAL asserts a wake-up interrupt when it reaches a zero count. The microprocessor wakes up sufficiently to determine if hardware needs to be awake at the next slot or to service a key-press event. If neither of these conditions is met, the software ensures that hardware can remain asleep by keeping the SLEEP_N signal active during the warm-up count down (via the WU TIME counter). At this time, the software estimates the number of sleep clocks needed to sleep in the next catnap based on several factors such as next catnap length, asynchronous lag in the slow clock, drift and truncation editors that arise from the use of sleep clock to approximate a multiple of PN roll. The exact calibration procedure was summarized above and is further detailed below. At time tS: when the WU TIME counter expires, a new value obtained in the previous step is loaded into the SLEEP_INTERVAL counter. The WU_TIME counter is a recomputed constant specified by a RF hardware warm-up requirements. The microprocessor goes back to sleep awaiting the wake-up interrupt from the next catnap. At time t6: If however there are any pending interrupts to be serviced or if this is the last catnap allowed in this sleep cycle, the hardware is woken up to be ready for the next slot by causing the SLEEP_N pin to go inactive at the wake-up interrupt. While the WUTIME counter counts down, the analog and RF components warm up. At time t7: theWU_TIME counter expires indicating the end of the last catnap and the SLPCHIPX8 regime is turned on at time t8. As a side note, the total time elapsed during all the catnaps, denoted by TB = t7 - t3, will be close to integer multiple of sleep clocks. Due to the several factors mentioned previously that are used in the sleep calibration, there will usually be a residual amount of time (a fraction of sleep clock) for which the subscriber station needs to still remain asleep. This fractional sleep clock (denoted by Tc) is converted into chips units and programmed into the CHIPX8_SLEEP_TIME that starts counting down clocked by the SLPCHIPX8. At time t9: the CH1PX8__SLEEP TIME expires, and the hardware turns on theRXCHIPXS at time too. The last time duration of interest is Tc - t9-t7. Thus, one of the major goals of the calibration process is to ensure that the sleep cycle length ASLEEP "‘ '‘A '‘ TB + Tc be a multiple of 26.67 ms. As mentioned earlier, the sleep crystal is a low frequency and inexpensive oscillator, and therefore may have high frequency errors (on the order of 200 ppm) due to factors such as temperature, aging and part tolerance. To meet a strict real-time deadline that is stipulated in the sleep mechanism of the IS-95A standard, it is important to have a good up-to-date estimate of the frequency of sleep clock before putting the subscriber station to sleep. A "Frequency Error Estimation circuit" (FEE) is used to provide running estimates of the frequency of slow clock. The FEE is used in the calibration in the following two different, but related ways. The effective frequency of the slow clock Fsc lies in the30-60 kHz range, the exact value of which is specified by the subscriber station manufacturer. It is convenient to make the calibration independent of the exact sleep clock, hence the FEE is initially used to estimate the frequency of the slow clock every time the subscriber station is powered up. The basic principle underlying the FEE is to count the number of chips (which is a very stable clock tracking the system timing) that have elapsed in a slow clock period. As an example, assume that the manufacturer has chosen an oscillator whose actual frequency is F’:’, =32. 76 KHz. Then, each sleep clock will have N':!’. =‘ 300. 073 chipx8's/sleep clock. In order to accommodate the fractionalchipxS's of significance in the counting process, the FEE actually counts the number of chips in L = 255 sleep clocks. The FEE continuously provides the chipxS count once FFF every L sleep clocks as long as the subscriber station is awake. As the accuracy of FEE is limited to only 1 chipxS in L’’’ slow clocks, the resulting maximum quantization error is = 1. 44 Hz (24 ppm) at F’sc "‘ 60 kHz. In order to smooth out the quantization error, a moving average window filter (MAW) of length L’'‘‘ ‘- 256 FEE samples is used, which provides estimates of F’'‘. with near-zero quantization error. The filter length is a compromise between quantization editor and response time. The advantage of using a MAW filter instead of integrate-and-dump type of averaging is that the MAW filter has a faster response for changes in the input frequency as it is updated with every FEE sample. Specifically, MAW provides one output every FEE output where as the integrate-and-dump filter gives one output every L’"‘ FEE samples. If Nap’s’ is the output of the MAW filter operating on the FEE outputs, then the initial estimate of the sleep clock frequency at power-up can be computed as: It is convenient to perform all the computations based on a constant nominal sleep clock frequency, rather than the variable F’'‘,. Hence, a nominal frequency is derived from the actual F’:’., such that: =L-P’r/75jx75 Hz Eq. 2 is a multiple of 75. Jan (x) respectively denote the integer and fractional portions of X Because of this choice, the manufacturer specific frequency can deviate from the nominal frequency as much as ±75/2Hz{± 600ppm) and still be mapped to the same nominal frequency. The dynamic frequency of sleep crystal is herein denoted by F’. After the initial use of FEE to estimate (Fsr,Fsr) is also used during the slotted operation to estimate the difference [F’’. -F’’’-) using the MAW. The computations performed using the nominal slow clock frequency F’.’. are adjusted to account for the errors (1) due to difference in nominal and actual slow clock frequencies (F’:’.-F’fJ and (2) due to temperature variations [F’’ --’sr/s "‘i’ ‘"‘‘ "drift compensations" defined as follows : "Fixed Drift Compensation (FDC)" that adjusts for the fixed, known error (F’:’. -FSV) incurred by using F’’, instead ofF’:’,. The FDC needed per each PN roll can be shown to be equal to: Under the assumption that the sleep crystal is operating at its nominal frequency of F’:’. Hz, there will be Fc’g/’sr chipx8's/nom_sleep clock. Then, the amount error incurred in chips for each nominal sleep clock when the sleep crystal is in reality operating at F’:’- Hz is The chipxS error per PN roll or FDC of Eq. 3 is obtained by multiplying the preceding expression by: F’’’’nom_SC/sQcxTi,’ sQc/PN roll. The relationship between the two drift compensations is shown in FIG. 4. The sum of DDC and FDC constitutes the total drift compensation needed to adjust F’:’ the based computations. Note that instead of these two separate drifts, a single "total drift" can be defined based directly on the difference of the dynamic and nominal frequencies (F’’-F.’fO- However, the advantage of splitting the drift compensation is that the dynamic drift tends to have a small magnitude that can be filtered (if so desired) with out saturation and overflow problems. At the beginning of each catnap, the catnap duration is rationed into (1) a maximum possible integer number of nominal sleep clock's that will be loaded into the SLEEPJNTERVAL and WU TIME registers and (2) a fractional sleep clock that is stored and accumulated in the subsequent catnaps in a variable called "residual tick counter/' RTCK Whenever RTCK "overflows" into an integer slow clock, it is reduced back to a fractional sleep clock, while the integer sleep clock is accounted in the SLEEP_INTERVAL register. During the sleep cycle, the subscriber station sleeps only for (SLEEPJNTERVAL futile) slow clocks in each catnap which is represented by the duration TB in FIG. 1 When it is time to wake up at the end of the last catnap, the final contents of RJCK represent the fractional slow clock duration that the subscriber station needs to sleep to make the sleep cycle a multiple of PN roll. This is achieved by programming the CHIPX8_SLEEP_TIME counter with the value of RICK ‘hat makes up for the time Tc- The CHIPX8_SLEEP_TIME counter can accommodate a maximum of 3 sleep clock's when the frequency is lowest (-32kHz), justifying our effort to keep RTCK under a sleep clock. Since by definition RTCK represents the extra time subscriber station needs to sleep, it is important to make sure that it remains positive. Sleep computations are done at the constant nominal slow clock frequency, hence there is a need to account for the difference in the nominal and (the real) dynamic slow clock frequencies via the total drift compensation, FDC + DDC of the previous section. In practice, the DDC as computed in Eq. 5 at the end of an access attempt/call is used to initialize a second-order feed back loop that is designed to minimize the calibration error. For subsequent sleep cycles, the DDC is derived from the feedback loop as M’ill be explained below. 1) Before every sleep cycle (tl): a) If there enough time lo sleep before the next combiner PN rolf, divide the sleep duration into multiple catnaps of lengths C], C2... CM (i-e- there are M catnaps), such that ASLEEP "‘ CJ + C2 +...Cv). 2) Before every sleep cycle (tl): Latest frequency drift estimates are obtained: a) If (first sleep cycle after end of access/call/analog), initialize the feed back loop with DDC of Eq. 4. b) The timing of signals provided by the base station has a very high accuracy. Accordingly, any error made in a previous estimate of the dynamic frequency (perhaps arising due to truncation effects or temperature or aging-induced frequency drifts) appears as a slew in the timing of the incoming signal. Slew, herein, indicates the timing difference or offset between the timing of signals received from the base station and internal timing within the mobile station after wakeup from a sleep period. c) Compute DDC from feedback loop. 3) Before every catnap(tl, t4): Before the first catnap(tl) or upon wake- up on each subsequent catnaps (t4), if the subscriber station is allowed to sleep for the next catnap, the following calibration procedure is undertaken : a) If (first catnap): initialize SLEEP_’COUNTER and RTCK : SLEEP COUNTERED RTCK’O b) If (second catnap): By now, since subscriber station has already slept for an extra lime T’ (which is generally not an integer sleep clock), remove that amount from residual tick counter: RTCK -’ RTCK TA c) c) Split catnap length C,n into integer and fractional nominal e) If (RTCK "overflows") into an integer sleep clock, reduce it to a fractional sleep clock and account for the integer portion in the SLEEP’COUNTER register: SLEEP_COUNTER SLEEP_COUNTER RxcK’ ] ‘- RTCK g) If (first catnap) : before programming for the first catnap (at time tl of Figure 3), the value of the extra time TA(==_-lisle clock's) that subscriber station sleeps is not yet known for use in calibrating the asynchronous sleep clock. If subscriber station has to wake up in the first catnap itself, the residual ticks need to be positive. To be on the safe side, adjust SLEEP_COUNTER and RICK SO as to sleep for two sleep clock's less in the first catnap: SLEEP_COUNTER’ - 2 + SLEEP_COUNTER RTCK 4) Time to wake up (t7): In the last catnap, as the WU TIME is counting down, the following computations are done: a) If (first catnap): If subscriber station is required to wake-up after the first catnap (see 3. g). the control does not get to 3. b where an adjustment is made for TA- SO the time x’ is accounted for in the residual ticks as: RTCK b) The CHIPX8_ SLEEP TIME is loaded with RTCK in (chips) and counted down at chipxS, to eventually wake up the subscriber station. 5) Re-acquisition upon wake up (too): a) The preceding calibration process ensures that the subscriber station sleeps for an integer number of FN rolls with very high accuracy (depends on the drift estimation). Consequently, the searcher should find the pilot with minimal offset relative to its position before sleep. Any error in the drift compensation shows up as "re-acquisition slew'b) The re-acquisition slew is stored to be used later in the next sleep cycle to run the feedback loop to modify or correct the DDC as will be shown in the next section. As noted above, the FEE is initially used to estimate the manufacturer specific sleep crystal's frequency F’’- from which the nominal frequency F’:’ derived. After the initial frequency estimation, if the subscriber station goes to the access/traffic channels/AMPS system, its internal temperature could increase considerably resulting in the dynamic frequency F’’’ to differ from its initial estimate. To handle this situation, the FEE is used to estimate the dynamic frequency drift every time the unit returns to the slotted-paging mode. However, this 'one time'‘ estimation of the dynamic drift at the beginning of slotted mode is not typically sufficient since the change in the frequency may occur over several sleep cycles as the unit cools off to its ambient temperature. Furthermore, changes in ambient temperature occur as well. It can be shown that a given error made in the drift compensation of the calibration results in a proportional pilot-drift (or re-acquisition slew) on wake up. For example, if the subscriber station has to sleep for and a calibration error resulted in only worth of sleep, the searcher will see the pilot drift by upon wake up. This fact is utilized in setting up a feedback loop that adaptively modifies the dynamic drift compensation (DDC) to minimize any error. FIG. 5 is a functional block diagram of the feedback loop. The calibration process described above is performed by a sleep calibration unit 200, which accepts the following four external inputs: 1. Slow crystal's dynamic frequency F!.’. , which is to be tracked, 2. Nominal slow clock frequency F!’. , a constant after the power-up estimation, 3. Fixed drift compensation Ni-oc- a constant after power-up estimation, and 4. Dynamic drift compensation NODC. which is the tracking variable. The sleep calibration unit employs these values in the sleep calculation equations described above to determine when the wake up other components of the mobile station for receiving paging signals or for handling other required tasks. As part of the sleep calculations, the sleep calibration unit counts cycles of the slow sleep clock during sleep periods. The sleep cerebration unit eventually outputs a wake up signal that is used by other components of the mobile station. The sleep calibration unit is employed with a feedback loop provided to compensate for drift in the slow clock crystal frequency so that the wake up signal is issued in synchronization with paging signals issued by the base station to minimize pilot reacquisition time. Hence, the aim of the feedback mechanism is to use F’’, NFDC NDDC to derive an adjusted value for NDDC (used in the sleep calculations described above) to compensate for changes in the slow crystal frequency F’f.. FIG. 5 also shows a conceptual flip-switch (FS) 202 that determines the source of NDDC- Very time the subscriber station leaves the slotted-paging mode (due to reasons detailed above) the switch is set to position 'A\ Consequently, the FEE supplies the initial estimate of the dynamic drift once the station comes back to the slotted-paging mode. After thus initializing the loop, the switch is moved to position 'B' and stays there as long as the unit is in slotted-paging mode. While in position B, a loop filter 204 supplies a corrected estimate of NDDC- At each paging slot, the mobile station performs a pilot re-acquisition process to reacquire the pilot signal from the nearest base station. Once the pilot is reacquired, a precise timing value is received from the base station representative of the true time. As noted above, any offset between the timing values provided by the base station ad timing values as detennined within the mobile station is slew. The amount of slew is detemnined based upon a comparison of the respective timing signals of the mobile station and the base station. The slew is evaluated as a slew per PN roll. A signal representative of the slew per PN roll is applied to the feedback loop filter every sleep cycle. The loop filter calculates an adjusted value for the NDDC based upon the value of the slew/PN roll and from predetermined loop values described below. The adjusted value of NDDC is then applied to the SLEEP COUNTER as described above in section 3.d to compensate for any drift in the sleep mode clock. Note that the value for NDDC is not applied directly to the loop filter. Rather, only the current value of the slew is applied. Nevertheless, with proper selection of the predetermined values used in the loop filter, the filter outputs an adjusted value of NDDC- The adjusted value is determined by the loop filter so that the amount of slew in the next pilot reacquisition cycle should be less than before. With repeated iterations, NDDC converges on a substantially fixed numeric value having a value sized to ensure that the slew is near zero. Iterative reduction of the slew to near zero typically occurs very quickly following the re-entry of the mobile station into the slotted-paging mode. Thereafter, the feedback loop provides any slight adjustments to NDDC to maintain the slew near zero. In this manner, the wake up signal output by the sleep calibration unit remains substantially in synch with paging slots of the base station so that pilot reacquisition time is minimized. The appropriate values for use in the feedback loop to reduce the slew to near zero and to maintain it near zero depend upon the particular characteristics of the mobile station, the sleep clock and the overall wireless system and are determined, for each particular embodiment, via routine experiments or other conventional techniques. Also, the choice of the order of the loop filter is dependent on the type of input frequency transient that needs to be tracked. If the slow crystal only has a constant frequency uncertainty, a first order loop is sufficient to track the constant frequency offset. However, in practice the frequency transient has a parabolic shape which makes a second or third order loop filter more desirable. For small slot-cycle-indices most often used in practice (SCI=0,1,2), the frequency transient is approximated very well by a simple ramp function, which is tracked wide minimal steady state error by a second order loop. If the loop is iterated every sleep with the slew S where B’ and (‘ can be chosen according to the input signal and noise characteristics. The "noise" in the loop arises due to the fluctuations in the pilot position in a multi-path and fading environment. The expressions for the sampled loop gains given in Eq. 5 are valid under the assumption that the loop is uniformly sampled, i. e., if and only if the loop iteration interval TSLEEP remains constant. For a given SCI, the sleep duration can be expressed as: TSLEEP =2' x 1.28 -TACTIVE. where TACTIVE is the time spent by subscriber station demodulating the paging channel when it is awake. Since Tanker depends on the length of the paging channel messages, there is no guarantee for some implementations that TSLEEP is a constant. Consequently, for those implementations, because the loop is non-uniformly up dated in time, the continuous time feedback loop approximation to a sampled loop that gave rise to Eq. 9 may require adjustment. Although the sleep cycle duration varies randomly varying, it is at substantially least guaranteed to be a multiple of PN roll. This fact is exploited to formulate a loop configuration with a frequency error defined as slew/PN roll (S The loop gains so computed for a single PN roll sleep cycles can be used for other sleep lengths TSLEEP while keeping in mind that the effective loop noise band-width is no longer Bj and is dependent on the SCL The exemplary embodiments have been primarily described with reference to block diagrams and flow charts illustrating pertinent features of the embodiments. As the flow charts, each step therein represents both a method step and an apparatus element for implementing the method step. The apparatus element may represent a means for implementing the method step, an apparatus for implementing the method step or other structural element for implementing the method step. It should be appreciated that not all components of a complete implementation of a practical system are necessarily illustrated or described in detail. Rather, only those components necessary for a thorough understanding of the invention have been illustrated and described. Actual implementations may contain more components or, depending upon the implementation, fewer components. The description of the exemplary embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art and the generic principles defined herein may be applied to other embodiments without the use of the inventive faculty. Thus, the invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein. WE CLAIM: 1. A method for compensating for frequency drift within a sleep clock signal used during a slotted paging mode of operation of a wireless mobile station, said mobile station in periodic communication with a base station providing timing signals, said method comprising the steps of: determining an initial frequency of the sleep clock signal following power-up of the mobile station; determining a fixed frequency drift compensation factor representative of a difference between the initial frequency of the sleep clock signal and a pre-determined nominal frequency ; estimating a dynamic frequency error compensation factor representative of a difference between the initial frequency and a current frequency of the sleep clock signal; and iteratively updating the dynamic frequency error compensation factor during the slotted mode of operation by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew. 2. The method as claimed in claim 1 wherein the step of determining the nominal frequency of the sleep clock signal is performed once following each power up of the mobile station. 3. The method as claimed in claim 1 wherein the step of estimating the dynamic frequency compensation factor is performed once for each entry into the slotted mode of operation. 4. The method as claimed in claim 1 wherein the step of determining a new value for the dynamic frequency compensation factor is performed once each cycle of the sleep clock signal. 5. The method as claimed in claim 1 wherein the feedback loop includes a loop filter represented by: wherein BL is a predetermined loop noise bandwidth value, ^ is a predetermined damping ratio and wherein a length of the sleep period is a multiple of The which is a predetermined time period. 7. The method as claimed in claim 1 wherein the order of the loop filter is selected based upon a degree of uncertainty in the frequency of the sleep clock signal. 8. The method as claimed in claim 7 wherein the frequency of the sleep clock signal is constant and wherein a first order loop in employed. 9. The method as claimed in claim 7 wherein an uncertainty in the sleep clock signal is represented by a parabolic function and wherein the loop is at least a second order loop. 10. The method as claimed in claim 1 wherein the wireless mobile station is configured to operate in both the slotted paging mode and within an AMPS mode and wherein a frequency error estimation circuit is employed to estimate a new value for the dynamic frequency error compensation factor subsequent to each transition from the AMPS mode to the slotted paging mode. 11. The method as claimed in claim 1 wherein the slew is determined by periodically receiving timing signals from the base station and comparing the timing signal from the base station with timing signal generated within the mobile station. 12. A device for compensating for frequency drift within a sleep clock signal used during a slotted paging mode of operation of a wireless mobile station, said mobile station in periodic communication with a base station providing timing signals, said device comprising: means for determining an initial frequency of the sleep clock signal following power-up of the mobile station; means for determining a fixed frequency drift compensation factor representative of a difference between the initial frequency of the sleep clock signal and a pre-determined nominal frequency; means for estimating a dynamic frequency error compensation factor representative of a difference between the initial frequency and a current frequency of the sleep clock signal; and means, operative during the slotted mode of operation, for iteratively updating the dynamic frequency error compensation factor by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew. 13. The device as claimed in claim 12 wherein the means for determining the nominal frequency of the sleep clock signal operates once following each power-up of the mobile station. 14. The device as claimed in claim 12 wherein the means for estimating the dynamic frequency compensation factor operates once for each entry into the slotted mode of operation. 15. The device as claimed in claim 12 wherein the means for determining an amount of slew in the sleep clock signal and for then determining a new value for the dynamic frequency compensation factor operates once each cycle of the sleep clock signal. 16. The device as claimed in claim 12 wherein the loop filter is represented by: 17. The device as claimed in claim 12 wherein the loop filter is represented by: wherein B^ is a predetermined loop noise bandwidth value, is a predetermined damping ratio and wherein a length of the sleep period is a multiple of TpN which is a predetermined time period. 18. A device for compensating for frequency drift within a sleep clock signal used during a slotted paging mode of operation of a wireless mobile station, said mobile station in periodic communication with a base station providing timing signals, said device comprising: an initial frequency determination unit; a fixed frequency drift compensation factor determination unit; a dynamic frequency error compensation factor determination unit; and a feed back unit, operative during the slotted mode of operation, for iteratively updating the dynamic frequency error compensation factor by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew.

Full Text

The invention generally relates to mobile communication systems and in particular to techniques for compensating for frequency drift in a low frequency clock employed during a sleep period between paging slots within a mobile station of a mobile communications system.
Description of the Related Art
Certain state of the art wireless communication systems, such as Code Division Multiple Access (CDMA) Systems employ slotted paging to allow mobile stations to conserve battery power. In a slotted paging system, paging signals are transmitted from a base station to particular mobile stations only within assigned paging slots separated by predetermined intervals of time.
Accordingly, each individual mobile station may remain within a sleep mode during the period of time between consecutive paging slots without risk of missed paging signals. Whether any particular mobile station may switch from an active-mode to a sleep mode depends, however, upon whether the mobile station is currently engaged in any user activity such as processing in put commands entered by the user or processing a telephonic communication on behalf of the user. Assuming though that the mobile station is not currently engaged in any processing on behalf of the user, the mobile station automatically powers down selected internal components during each period of time between consecutive slots. One example of a slotted paging system is disclosed in U. S. Patent No. 5,392,287, entitled "Apparatus and Method for Reducing Power Consumption in a Mobile Receiver issued February 21, 1995, assigned to the assignee of the present invention and incorporated by reference herein.

Thus, within a slotted paging system, a mobile station reduces power consumption by disorienting power from selected internal components during a sleep period between consecutive slots. However, even during the sleep period, the mobile station must reliably track the amount of elapsed time to determine when the next slot occurs to permit receive components of the mobile station to power up in time to receive any paging signals transmitted within the slot. One solution to this problem is to operate a high frequency clock throughout the sleep period and to track the amount of elapsed time using the high frequency clock. This solution allows the sleep period to be very precisely tracked using the high frequency clock. However, considerable power is consumed operating the high frequency clock and optimal power savings therefore are not achieved during the sleep period.
Hence, it would be desirable to instead employ an alternate low frequency, low power clock during the sleep period to further reduce power consumption. However, low frequency, low power clock signals typically suffer from considerable frequency drift such that the amount of elapsed time during the sleep period cannot be precisely determined. Frequency drift within a mobile station can be particularly significant as a result of temperature variations within the mobile station either as a result of changes in operation of components of the mobile station or as a result of ambient conditions of the mobile station. For example, during an extended telephone call, components of the mobile station may heat to 87 degrees Celsius. During an extended period of inactivity, the temperature of the components may cool to an ambient temperature of, perhaps, 25 degrees Celsius. Moreover, if the user places the mobile telephone in either a very hot or very cold location, the temperature change may be even more

significant. Typical low power, low frequency clock signal generators are significantly affected by even relatively minor temperature changes and are even more strongly affected by such broad changes in temperature. Indeed, the amount of drift in a typical low power, low frequency clock signal is sufficiently great such that if used by itself to calculate the elapsed time, there is significant risk that the mobile station will not be reactivated in time to power up components to detect a paging signal transmitted within a next paging slot. Accordingly, important paging signals maybe missed possibly resulting in missed phone calls and the like.
Hence, when using a low-frequency clock signal to track time during a sleep period, the mobile station is typically configured to return to an active mode by activating a high frequency clock signal well in advance of a next expected paging slot to thereby avoid possible timing errors. Thus, for example, if the paging slots occur ever 26. 67 milliseconds, the mobile station may be programmed to activate the high frequency clock and to power up receive components after only, for example, 26 milliseconds of sleep to ensure that the next paging slot is not missed. Hence, optimal power savings are not achieved.
One technique that has been proposed for compensating for timing errors inherent in low frequency, low power clock signal generators is to adapt a length of a current sleep period based upon a timing accuracy of a previous sleep period. More specifically, if a previous sleep period was determined to be too long due to timing errors in the low power, low frequency clock generator, the mobile station is programmed to wake up earlier in the current sleep period. To determine whether a sleep period is too long or too short, the mobile station attempts to detect a unique word within a received paging signal, such as a message preamble which signifies

the beginning of an assigned slot. If the unique word is not detected, the mobile station concludes that it woke up too late and therefore the sleep duration is decreased for subsequent sleep periods. If the unique word was properly received, the mobile station either woke up on time or wake up too early and the sleep duration is in creased slightly for the subsequent sleep period. One problem with the aforementioned technique is that it assumes that any failure to detect the unique word is a result of a timing error. However, there may be other reasons besides the duration of the sleep period that the unique word was not correctly received and demodulated, such as poor communication channel quality conditions. Moreover, even if failure to detect the unique word was a result of a timing error rather than other communication errors, the system still does not precisely correct for errors in the low power, low frequency clock signal and therefore does not provide for optimal power savings.
A significant improvement is provided in U. S. Patent Application Serial No. 09/134,808,entitled "Synclironization of a Low Power Oscillator with a Reference Oscillator in a Wireless Communication Device Utilizing Slotted Paging", filed August 14,1998 and assigned to the assignee of the present invention. In the aforementioned patent application, timing errors are corrected without relying upon the failure to receive portions of transmitted signals.
Rather, the system includes a frequency error estimation unit for directly estimating the frequency of the low power, low frequency clock. In one example described in the patent application, the frequency error in the low frequency clock is determined by timing the low frequency clock using a high frequency clock during periods of time when the high frequency clock is active. For example, during each paging slot when the high

frequency clock signal of the mobile station is activated, the frequency error in the low frequency clock is calculated based upon the high frequency clock. Additionally, the system operates to synchronize the activation of the high frequency clock very precisely to transitions in the low frequency clock signal to further reduce errors.
Although the system of the aforementioned patent application provides a significant improvement over systems which rely on the detection of unique words of signals transmitted to the mobile station, considerable room for improvement remains. To permit the mobile station to respond promptly to any keys that have been pressed by a user during a sleep period, it is often desirable to subdivide the sleep period into a sequence of sub-periods, also referred to herein as "catnaps". After each catnap, selected components of the mobile station are powered up sufficiently to detect whether a key on the keypad has been pressed and, if so, the sleep period is aborted and other components of the mobile station are powered up as needed to respond to the'pressed key. The duration of the catnaps are typically not an integer number of cycles of the low frequency sleep mode clock. Accordingly, considerable truncation errors can occur if the low frequency clock, by itself, is employed to time the catnaps. Hence, it would be desirable to provide a system for timing sleep periods using a low frequency clock in such a manner to eliminate substantial truncation errors and aspects of the invention are directed to this end. Also, because the frequency error is calculated only while the mobile station is in an active-mode, it may not properly detect frequency errors occurring during extended sleep periods during which time the temperature of the low frequency clock signal generator decreases significantly. Accordingly, even with the improved system of the patent application, the

high frequency clock signal must be usually be activated somewhat in advance of the next expected paging slot to account for remaining timing errors. Hence, optimal power savings are not achieved. It would be also preferable to provide a system wherein frequency drift is estimated effectively to permit an active mode high frequency clock to be turned on as close as possible to the next paging slot to permit maximum power savings during the sleep period and to permit easy reacquisition of a paging signal and it is to these ends that other aspects of the present invention are also directed.
SUMMARY OF THE INVENTION
In accordance with a first aspect of the invention, a method is provided for tracking the length of a sleep period within a mobile station using a sleep clock. The method operates to precisely calibrate portions of the sleep period. In accordance with the method, a sleep period is initiated with the sleep period subdivided into a sequence of sub-periods each of known duration but wherein the durations of the sub-periods are not necessarily integer multiples of cycles of the sleep clock. Elapsed time is tracked within each individual sub-period of the sleep period using an integer sleep counter which tracks whole cycles of the sleep clock. Any remaining fractional portions of the cycles of the sleep mode clock not accounted for by the integer sleep counter are tracked using a fractional sleep counter, with the fractional sleep counter accumulating remaining fractional portions of sleep clock cycles from one sub-period to the next.
In an exemplary embodiment of the first aspect of the invention, the sub periods of the sleep period are "catnaps". Within each catnap, the integer sleep counter is incremented downwardly on each cycle of the sleep clock. When the integer sleep counter reaches 0, the catnap is deemed to be

complete. When the catnap is complete, a keypad of the mobile station is checked to determine whether a key has been pressed and, if so, the sleep period is terminated. Whenever the fractional counter overflows, a current value of the integer sleep counter is increased by a integer overflow portion of the fractional sleep counter such that the integer counter then accounts for the over flow. A current value of the fractional sleep counter is reset to be equal only to the remaining fractional portion, if any, of the previous fractional sleep counter value such that the fractional sleep counter continues to track remaining fractional portions of cycles of the sleep mode clock.
In accordance with a second aspect of the invention, a method is provided for compensating for frequency drift within a sleep clock signal used to time sleep periods during a slotted paging mode of operation of a wireless mobile station wherein the wireless mobile station receives signals from a base station having high timing accuracy. The method operates to iteratively adjust an estimate of the frequency drift during a sleep mode to enable effective frequency drift compensation. In accordance with the method, an initial frequency of the sleep clock signal is determined following power-up of the mobile station. A fixed frequency drift compensation factor representative of a difference between the initial frequency of the sleep clock signal and a predetermined nominal frequency (that eliminates truncation error) is then determined for computational convenience. A dynamic frequency error compensation factor representative of a difference between the initial frequency and a current dynamic frequency of the slow clock signal (which may vary due to temperature or aging) is estimated. Then, during the slotted mode of operation, the following steps are iteratively performed. The dynamic

frequency error compensation factor is updated by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew.
In an exemplary implementation, the sleep period length is converted into the number of sleep clocks using the dynamic frequency as the initial estimate. After each wakeup from a sleep period, the mobile station searches for an incoming signal from the base station. As timing is maintained at the base station with very high accuracy, any error made in the initial estimate of dynamic frequency (arising due to truncation effects or temperature-and aging induced frequency drifts) will show up as a "slew" in the timing of the in coming signal. The quantity "slew" indicates the timing difference or offset that the mobile perceives after wakeup from sleep. Then a new value for the dynamic frequency compensation factor is determined by applying a value representative of the amount of the slew to a loop filter.
In a preferred implementation, the mobile station is configured to implement both the improved calibration method and the improved frequency drift estimation method. Apparatus embodiments of the invention are also provided.
BRIEF DESCRIPTION OF THE DRAWINGS
The features, objects, and advantages of the invention will become more apparent from the detailed description set forth below when taken in conjunction with the drawings in which like reference characters identify correspondingly throughout and wherein:

FIG. 1 is a timing diagram illustrating a pair of consecutive sleep periods, each including one or more catnap periods, tracked in accordance with an exemplary method of the invention.
FIG. 2 is a flow chart illustrating the exemplary method of the invention.
FIG. 3 is a timing diagram illustrating various clock signals utilized by the exemplary method of FIG. 2.
FIG. 4 is a vector diagram illustrating certain timing values processed by the method of FIG. 2.
FIG. 5 is a block diagram illustrating a feedback loop employed by the exemplary method of the invention to estimate frequency drift. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
Referring to the figures, an exemplary embodiment of the invention will now be described. Initially, a method by which the exemplary embodiment operates to time a sleep period using a sleep-mode clock and to calibrate the end of the sleep period precisely with a next paging slot will be described with reference to FIGS. 1-3. The method operates to precisely calibrate the length of the sleep period despite frequency drift which may occur during the sleep period. Then, a method by which the exemplary embodiment operates to estimate the frequency drift will be described with reference to the remaining figures.
FIG. 1 is a timing diagram illustrating a pair of consecutive sleep periods 100 and 102 each subdivided into a set of sub-periods or "catnaps" generally denoted by reference numeral 104. During a period of time between each catnap, the mobile station wakes up only those components necessary to determine whether a key has been pressed on the key pad. In the example of FIG. 1, each sleep period includes only two catnaps. In other

implementations a different number of catnaps may be employed. Each sleep period is timed primarily using only a sleep-mode clock having a relatively slow frequency, such as a 32 kilohertz clock. As will be described, a transition-mode clock having a substantially higher frequency than the sleep-mode clock is employed at the beginning and end of the sleep period to help calibrate the length of the sleep period. The length of the sleep period is not necessarily an integer number of cycles of the sleep clock. Likewise, the lengths of individual catnaps are not necessarily integer multiples of the sleep clock. To account for fractional portions of the sleep-mode clock, a fractional counter is employed.
Also, the complete set of catnaps within the sleep period does not account for the entire period of time within the sleep period. Rather, an initial period of time Ta occurs prior to the start of the first catnap and a final period of time Tc occurs between the end of the last catnap and the end of the sleep period. The initial period Ta occurs because of the first catnap does not begin until a first edge of the sleep-mode clock is detected and the first edge with may be offset from the start of the sleep period. The final time period Tc is provided to permit the system to precisely calibrate the termination of the sleep period with a next paging slot by taking into account the fractional portions of sleep cycles counted using the fractional counter.
Referring now to FIG. 2, the method by which the mobile station deter mines the lengths of various catnaps and determines the amount of time Tc necessary to precisely terminate the end of the sleep period with the next paging slot will now be described. The mobile station initiates the sleep period at step 110. At step 112, the integer counter (I_COUNTER) and the fractional counter (F_COUNT) are both set to 0. Then, at step 114,

the first of a series of catnaps is initiated. The first catnap commences with a falling edge following the first detected rising edge of the sleep-mode clock which, as noted above, may be offset from the start time of the sleep period by an initial offset time Ta.
At step 116, the mobile station determines the number of cycles of the sleep clock within the current catnap based upon the length of the catnap. The length of the catnap is predetermined and values representative of the length may be stored in appropriate memory registers. Then, at step 118, the integer counter is reset to equal the previous value of the integer counter plus the integer number of cycles in the current catnap. Prior to the first execution of step 118, the integer counter is set to 0. Hence, following step 118, the integer counter is simply set to the number of whole cycles of the sleep clock occurring during the first catnap. At step 120, the fractional counter is set to equal the previous value of the fractional counter plus any fractional remainder of the cycles of the sleep mode clock in the catnap. Again, prior to the first execution of step 120, the fractional counter is initially set to 0 and hence, following step 120, the fractional counter is simply set to the fractional number of cycles remaining in the first catnap not accounted for by the integer number of cycles stored within the integer counter.
At step 122, if the current catnap is the first catnap, then the offset time Ta between the start of the sleep period and the start of the first catnap is determined. In the preferred implementation, the duration of the offset time is determined by activating a high frequency transition-mode clock prior to the commencement of the sleep period, then counting the number of cycles in the transition-mode clock occurring between the start of the sleep period and the start of the first catnap. Further details regarding the

transition-mode clock are provided in a co-pending U. S. Patent Application entitled "Method and Apparatus for Activating a High Frequency Clock Following a Sleep Mode within a Mobile Station Operating in a Slotted Paging Mode", filed contemporaneously herewith, assigned to the assignee of the present application, and incorporated by reference herein.
At step 124, the mobile station then determines whether the current cat nap is the second catnap and if so operates to subtract the initial offset time Ta from the current value of the fractional counter in step 126. Hence, during a second catnap, the mobile station resets the fractional counter to compensate for the initial offset time. Continuing, though, with processing occurring during of the first catnap, execution proceeds directly from step 124 to step 126 wherein the mobile station determines the frequency drift in the first catnap. The manner by which the frequency drift is estimated will be described below.
The estimate of the frequency drift includes both an integer portion (I_DR1FT) and a fractional remainder portion (FDRIFT). The integer portion represents the amount of frequency drift occurring within the catnap in whole cycles of the sleep-mode clock. The amount of frequency drift will not likely be precisely equal to an integer number of the sleep mode clock cycles. Any fractional remainder is represented by F_DRIFT. At step 128, the mobile station adds IDRIFT to I COUNT and also adds F_DRIFT to F_COUNT to thereby account for both the integer and fractional portions of the frequency drift. Following step 128, it is possible that the fractional counter will be greater than 1. Such may occur, for example, if the total of the fractional portion of the frequency drift determined at step 126 and the fractional portion of the duration of the catnap determined at step 120 collectively exceed one complete cycle of the

sleep mode clock. To ensure that the fractional counter remains between 0 and 1.0, the mobile station determines, at step 130, whether the F_COUNT is greater than 1 and, if so, step 132 is performed wherein the integer counter is incremented by 1 and the fractional counter is decremented bill. Following step 132, execution returns to step 130 wherein the mobile station again determines whether the fractional counter is greater than 1.0 and, if so, step 132 is repeated. In this manner, steps 130 and 132 are repeated in a loop until the fractional counter is reset to a value between 0 and 1.0.
On the other hand, following step 128, it is possible that the fractional counter will be less than 0. Such may occur if the frequency drift value is a negative value and is larger in magnitude than the fractional remainder determined at step 120. To ensure that the fractional counter remains between 0 and 1.0, the mobile station determines at step 134 whether F_COUNT is less than 0 and, if so, step 136 is performed wherein the integer counter is decremented by 1 and the fractional counter is incremented by 1. Following step 136, execution returns to step 134 wherein the mobile station determines whether the fractional counter is still negative and, if so, step 136 is repeated. In this manner, steps 134 and 136 are repeated in a loop until the fractional counter is reset to a value between 0 and 1.0.
At step 138, the mobile station accounts for any necessary wakeup time (or warm-up interval) required at the end of each catnap to allow the components of the mobile station to power up to detect whether any keys on the keypad have been pressed. Accordingly, at step 138, the mobile station determines the duration of the wakeup period in cycles of the sleep-mode

clock then subtracts the wakeup period from the value currently held with an integer counter. The length of the wake up period is predetermined and values representative of the length may be stored in appropriate memory registers.
Note that any fractional portion of the wakeup period is not separately accounted for. In other implementations, the wakeup period can be divided into an integer portion and a fractional portion with the fractional portion subtracted from the fractional counter as well.
Thus, following step 138, the integer counter contains a value indicating the number of cycles of the sleep-mode clock occurring between the beginning of the current catnap and the beginning of the wakeup period at the end of the catnap, adjusted, for example, to account for the frequency drift. Beginning at step 140, the mobile station times the catnap by subtracting 1 from the value of I_COUNT with each tick of the sleep-mode clock then, at step 142, checking to determine whether I_COUNT has reached 0. Once I__COUNT has reached 0, the point and time wherein components of the mobile station need to wakeup to facilitate any required processing at the end of the catnap has been reached.
As step 144, the mobile station then begins waking up those components and, upon completion of the wakeup period, performs any necessary fimctions such as determining whether any of the keys on the key pad have been pressed. If any key has been pressed, or if the mobile station, determines that any other processing is required, then the mobile station wakes up at step 146.
Depending upon the implementation, this may involve powering up all remaining components of the mobile station or perhaps powering up only those components required to perform the particular required

functions. In any case, the high-frequency clock is activated at step 146 and further sleep mode processing is terminated.
If, however, at step 144 the mobile station determines that no keys have been pressed and that no other action is required, then execution proceeds to step 148 wherein the mobile stations determines whether the just completed catnap was the last catnap of the sleep period. If not, then at step 150, the mobile station begins the next catnap causing execution to return to stepll6 wherein the mobile station determines the number of cycles of the sleep clock within the new catnap and proceeds as described above.
In this manner, until either a key has been pressed or until the last catnap has been completed, the mobile station executes steps 116-150 in a continuous loop. Note that, although the integer counter I_COUNT will always be equal to 0 at the beginning of each catnap loop (i. e., at step 116) the fractional counter FCOUNT will typically not be equal to 0 at the beginning of any catnap other the first. Rather, the fractional counter will retain whatever previous fractional count was held therein. In this matter, the fractional counter accumulates fractional portions of sleep cycles from one catnap to the next. Eventually the fractional counter will likely overflow, i. e., the fractional counter will at some point be set to a value greater than 1.0. If so, then during a first subsequent execution of step 130, the overflow is accounted for by incrementing ICOUNT by 1 and by decrementing F_COUNT by 1. In this manner, upon the completion of each catnap, the fractional counter will again be equal to some value between 0 and 1.0. Thus, only fractional remainders of sleep cycles are carried from one catnap to the next and all integer portions are accounted for within each individual catnap. In other words, the duration of each

catnap is calibrated to be within at least one sleep cycle of the intended catnap length.
Eventually, at step 148, the mobile station will detect that the just completed catnap is the last catnap and, if so. execution proceeds to step 152 or in the mobile station begins to account for the remaining period of time Tc necessary to wake up the receive components of the mobile station in time for the next paging slot. In some circumstances, only a single catnap will occur within the sleep period, hence the last catnap is also the first catnap. Such may occur, e. g., when the mobile station is woken up due to a key pad event occurring during the first catnap. Earlier it was noted that during a second catnap, at steps 124 and 126, the fractional counter is reset to account for the initial offset time Ty. However, if there is only a single catnap, stepl26 will not have been executed. Accordingly, the mobile station determines, at step 152 whether the just completed catnap was the only catnap and, if so, step 154 is performed to subtract the initial offset time from the current value of the fractional counter. In either case, execution proceeds to step 126 wherein the mobile station then reactivates the transition mode clock to time the remaining amount of time specified by the fi-actional counter and, when that period has elapsed, the mobile station then wakes up at step 146.
Thus, FIG. 2 illustrates a method whereby the mobile station precisely calibrates the length of the overall sleep period to wake up receive components of the mobile station just in time to receive a paging signal, if any, provided within the next paging slot. Hence, the receive componerits remain powered down for the maximum possible duration to thereby gain the maximum amount of power savings during the sleep period. Precise

calibration is achieved, in part, using the aforementioned fractional sleep counter which ac cumulates fractional portions of complete cycles of the sleep clock from one catnap to the next to permit those fractional portions to be ultimately ac counted for prior to wakeup of the receive components.
In the following, a specific example is described for use within a mobile station configured in accordance with IS-95A standard. According to the IS-95A standard, a CDMA mobile station or "subscriber station" operating in a slotted mode maximizes the standby time by going to sleep, based on a parameter. Slot Cycle Index (SCI). The subscriber station wakes up every (1. 28 * 2) sec to monitor its assigned 80 ms slot to receive pages. For example with SCI = 0, the subscriber station ideally remains awake for 80 ms and sleeps for 1.2 sec. As noted above, the station must wake up a sufficient amount of time ahead of the next slot boundary so as to take care of events such as radio frequency (RF) component warm-up, synthesizer stabilization, clock settling, CDMA pilot search and acquisition, finger reassignment and decoder warm up.
As shown in FIG. 3, in each sleep cycle the unit sleeps in catnaps to allow good response time if the user presses a key while it is asleep. The sleep cycle length and catnap length are chosen to be multiples of a pseudorandom number period (also known as PN roll) so that upon wake-up, pilot may easily be found. TPN may be, for example, 26.67 milliseconds. Each catnap is further divided into:(l)"sleep time," when the entire unit is put to sleep and (2) "warm-up time," when the RF and analog units are turned on for warm-up. When the subscriber station is asleep, the system time is approximately maintained by clocking the counters that keep track of sleep duration with a combination of the sleep clock for coarse timing (maximum resolution of 1/60k = 16.7 micro-sec) and the transition

mode clock (SLPCHIPX8) for fine timing (resolution of 1/(8*1. 2288e6) = 0.102 micro-sec).
An example of the events that constitute a sleep cycle is shown in FIG. 3. Waveform E within the figure marks each event in the sleep cycle as follows:
Before tl : When it is time to sleep, the software shuts off all unnecessary clock regimes except for the CDMA demodulator and a decoder clock regime, RXCHIPX8 (Waveform B).
A catnap (which is a multiple of 26.67 ms) is split into sleep time and warm-up time and programmed as the duration of the first catnap interval through the SLEEP’INTERVAL and WU_TME registers.
Software writes an ASIC SLEEP ARM bit of a SLEEP_CTL register, indicating that subscriber station must go to sleep on the next PN roll (indicated bytl).
All along, the sleep clock (Waveform D) runs asynchronous to a high frequency CDMA clock regime CHIPX8, while the SLPCHIPX8 (Wave- form C) is in sync with the RXCH1PX8, having been derived the same source,CHIPX8.
At time when a PN roll occurs, the RXCHIPX8 clock regime is disabled putting the subscriber station to sleep. It is this point onwards that it is desirable for the sleep period to be very close to multiples of 26.67 ms using counters SLEEP_INTERVAL and WU TIME running off the sleep clock. To account for the asynchronous sleep clock, a transition-mode counter called CHIPX8_SLEEP_TIME starts counting the SLPCHIPXS's that have elapsed from tl to the next rising edge of the sleep clock.

At time t2 : the rising edge of sleep clock occurs at which time the SLPCHIPX8 clock regime is disabled, freezing the CHIPX8__SLEEP_TIME, there by providing an estimate of the time duration (t2-tl) in chips units.
At time t3: after half a sleep clock duration, a SLEEP_N signal (Waveform A) goes low on the falling edge of the sleep clock causing the other digital, analog and RF components in the phone to transition to a low power mode. If there are Ng’ chips in a sleep clock cycle, the total time elapsed at this point of time is given by: TA ‘ (t2-tl) +(t3-t2) = {CHIPX8_SLEEP_TME +_Nsc} chips. It may be noted that from this definition, TA will be in the range of slow clock cycles. Subsequent catnaps are adjusted to account for this extra time slept owing to the asynchronous sleep crystal. Also a counter SLEEP_INTERVAL running off the sleep clock starts to counts down.
At time t4 : the counter SLEEP INTERVAL asserts a wake-up interrupt when it reaches a zero count. The microprocessor wakes up sufficiently to determine if hardware needs to be awake at the next slot or to service a key-press event.
If neither of these conditions is met, the software ensures that hardware can remain asleep by keeping the SLEEP_N signal active during the warm-up count down (via the WU TIME counter). At this time, the software estimates the number of sleep clocks needed to sleep in the next catnap based on several factors such as next catnap length, asynchronous lag in the slow clock, drift and truncation editors that arise from the use of sleep clock to approximate a multiple of PN roll. The exact calibration procedure was summarized above and is further detailed below.

At time tS: when the WU TIME counter expires, a new value obtained in the previous step is loaded into the SLEEP_INTERVAL counter. The WU_TIME counter is a recomputed constant specified by a RF hardware warm-up requirements. The microprocessor goes back to sleep awaiting the wake-up interrupt from the next catnap.
At time t6: If however there are any pending interrupts to be serviced or if this is the last catnap allowed in this sleep cycle, the hardware is woken up to be ready for the next slot by causing the SLEEP_N pin to go inactive at the wake-up interrupt. While the WUTIME counter counts down, the analog and RF components warm up.
At time t7: theWU_TIME counter expires indicating the end of the last catnap and the SLPCHIPX8 regime is turned on at time t8. As a side note, the total time elapsed during all the catnaps, denoted by TB = t7 - t3, will be close to integer multiple of sleep clocks. Due to the several factors mentioned previously that are used in the sleep calibration, there will usually be a residual amount of time (a fraction of sleep clock) for which the subscriber station needs to still remain asleep. This fractional sleep clock (denoted by Tc) is converted into chips units and programmed into the CHIPX8_SLEEP_TIME that starts counting down clocked by the SLPCHIPX8.
At time t9: the CH1PX8__SLEEP TIME expires, and the hardware turns on theRXCHIPXS at time too. The last time duration of interest is Tc - t9-t7.
Thus, one of the major goals of the calibration process is to ensure that the sleep cycle length ASLEEP "‘ '‘A '‘ TB + Tc be a multiple of 26.67 ms.

As mentioned earlier, the sleep crystal is a low frequency and inexpensive oscillator, and therefore may have high frequency errors (on the order of 200 ppm) due to factors such as temperature, aging and part tolerance. To meet a strict real-time deadline that is stipulated in the sleep mechanism of the IS-95A standard, it is important to have a good up-to-date estimate of the frequency of sleep clock before putting the subscriber station to sleep. A "Frequency Error Estimation circuit" (FEE) is used to provide running estimates of the frequency of slow clock. The FEE is used in the calibration in the following two different, but related ways.
The effective frequency of the slow clock Fsc lies in the30-60 kHz range, the exact value of which is specified by the subscriber station manufacturer. It is convenient to make the calibration independent of the exact sleep clock, hence the FEE is initially used to estimate the frequency of the slow clock every time the subscriber station is powered up.
The basic principle underlying the FEE is to count the number of chips (which is a very stable clock tracking the system timing) that have elapsed in a slow clock period. As an example, assume that the manufacturer has chosen an oscillator whose actual frequency is F’:’, =32. 76
KHz. Then, each sleep clock will have N':!’. =‘ 300. 073 chipx8's/sleep clock.
In order to accommodate the fractionalchipxS's of significance in the counting process, the FEE actually counts the number of chips in L = 255 sleep clocks. The FEE continuously provides the chipxS count once
FFF
every L sleep clocks as long as the subscriber station is awake.
As the accuracy of FEE is limited to only 1 chipxS in L’’’ slow clocks, the resulting maximum quantization error is = 1. 44 Hz (24 ppm) at F’sc "‘ 60 kHz. In order to smooth out the quantization error, a moving

average window filter (MAW) of length L’'‘‘ ‘- 256 FEE samples is used, which provides estimates of F’'‘. with near-zero quantization error. The
filter length is a compromise between quantization editor and response time. The advantage of using a MAW filter instead of integrate-and-dump type of averaging is that the MAW filter has a faster response for changes in the input frequency as it is updated with every FEE sample. Specifically, MAW provides one output every FEE output where as the integrate-and-dump filter gives one output every L’"‘ FEE samples. If Nap’s’ is the output of
the MAW filter operating on the FEE outputs, then the initial estimate of the sleep clock frequency at power-up can be computed as:

It is convenient to perform all the computations based on a constant nominal sleep clock frequency, rather than the variable F’'‘,. Hence, a
nominal frequency is derived from the actual F’:’., such that:
=L-P’r/75jx75 Hz Eq. 2
is a multiple of 75. Jan (x) respectively denote the integer and
fractional portions of X Because of this choice, the manufacturer specific frequency can deviate from the nominal frequency as much as ±75/2Hz{± 600ppm) and still be mapped to the same nominal
frequency.
The dynamic frequency of sleep crystal is herein denoted by F’.
After the initial use of FEE to estimate (Fsr,Fsr) is also used during the slotted operation to estimate the difference [F’’. -F’’’-) using the MAW. The

computations performed using the nominal slow clock frequency F’.’. are adjusted to account for the errors (1) due to difference in nominal and actual slow clock frequencies (F’:’.-F’fJ and (2) due to temperature variations
[F’’ --’sr/s "‘i’ ‘"‘‘ "drift compensations" defined as follows :
"Fixed Drift Compensation (FDC)" that adjusts for the fixed, known
error (F’:’. -FSV) incurred by using F’’, instead ofF’:’,. The FDC needed per
each PN roll can be shown to be equal to:

Under the assumption that the sleep crystal is operating at its nominal frequency of F’:’. Hz, there will be Fc’g/’sr chipx8's/nom_sleep clock. Then, the amount error incurred in chips for each nominal sleep clock when the sleep crystal is in reality operating at F’:’- Hz is

The chipxS error per PN roll or FDC

of Eq. 3 is obtained by multiplying the preceding expression by:
F’’’’nom_SC/sQcxTi,’ sQc/PN roll. The relationship between the two drift
compensations is shown in FIG. 4. The sum of DDC and FDC constitutes the total drift compensation needed to adjust F’:’ the based computations.
Note that instead of these two separate drifts, a single "total drift" can be defined based directly on the difference of the dynamic and nominal frequencies (F’’-F.’fO- However, the advantage of splitting the drift

compensation is that the dynamic drift tends to have a small magnitude that can be filtered (if so desired) with out saturation and overflow problems.
At the beginning of each catnap, the catnap duration is rationed into
(1) a maximum possible integer number of nominal sleep clock's that will
be loaded into the SLEEPJNTERVAL and WU TIME registers and (2) a
fractional sleep clock that is stored and accumulated in the subsequent
catnaps in a variable called "residual tick counter/' RTCK Whenever RTCK
"overflows" into an integer slow clock, it is reduced back to a fractional
sleep clock, while the integer sleep clock is accounted in the
SLEEP_INTERVAL register. During the sleep cycle, the subscriber station
sleeps only for (SLEEPJNTERVAL futile) slow clocks in each
catnap which is represented by the duration
TB in FIG. 1 When it is time to wake up at the end of the last catnap, the final contents of RJCK represent the fractional slow clock duration that the subscriber station needs to sleep to make the sleep cycle a multiple of PN roll. This is achieved by programming the CHIPX8_SLEEP_TIME counter with the value of RICK ‘hat makes up for the time Tc- The CHIPX8_SLEEP_TIME counter can accommodate a maximum of 3 sleep clock's when the frequency is lowest (-32kHz), justifying our effort to keep RTCK under a sleep clock. Since by definition RTCK represents the extra time subscriber station needs to sleep, it is important to make sure that it remains positive.
Sleep computations are done at the constant nominal slow clock frequency, hence there is a need to account for the difference in the nominal and (the real) dynamic slow clock frequencies via the total drift compensation, FDC + DDC of the previous section. In practice, the DDC as

computed in Eq. 5 at the end of an access attempt/call is used to initialize a second-order feed back loop that is designed to minimize the calibration error. For subsequent sleep cycles, the DDC is derived from the feedback loop as M’ill be explained below.
1) Before every sleep cycle (tl):
a) If there enough time lo sleep before the next combiner PN rolf, divide the sleep duration into multiple catnaps of lengths C], C2... CM (i-e- there are M catnaps), such that ASLEEP "‘ CJ + C2 +...Cv).
2) Before every sleep cycle (tl): Latest frequency drift estimates are
obtained:
a) If (first sleep cycle after end of access/call/analog), initialize the feed back loop with DDC of Eq. 4.
b) The timing of signals provided by the base station has a very high accuracy. Accordingly, any error made in a previous estimate of the dynamic frequency (perhaps arising due to truncation effects or temperature or aging-induced frequency drifts) appears as a slew in the timing of the incoming signal. Slew, herein, indicates the timing difference or offset between the timing of signals received from the base station and internal timing within the mobile station after wakeup from a sleep period.
c) Compute DDC from feedback loop.
3) Before every catnap(tl, t4): Before the first catnap(tl) or upon wake-
up on each subsequent catnaps (t4), if the subscriber station is
allowed to sleep for the next catnap, the following calibration
procedure is undertaken :

a) If (first catnap): initialize SLEEP_’COUNTER and RTCK : SLEEP COUNTERED
RTCK’O
b) If (second catnap): By now, since subscriber station has already slept for an extra lime T’ (which is generally not an integer sleep clock), remove that amount from residual tick counter: RTCK -’ RTCK TA
c) c) Split catnap length C,n into integer and fractional nominal

e) If (RTCK "overflows") into an integer sleep clock, reduce it to
a fractional sleep clock and account for the integer portion in
the SLEEP’COUNTER register:
SLEEP_COUNTER
SLEEP_COUNTER RxcK’ ] ‘- RTCK g) If (first catnap) : before programming for the first catnap (at time tl of Figure 3), the value of the extra time TA(==_-lisle clock's) that subscriber station sleeps is not yet known for use in calibrating the asynchronous sleep clock. If subscriber station has to wake up in the first catnap itself, the residual ticks need to be positive. To be on the safe side, adjust SLEEP_COUNTER and RICK SO as to sleep for two sleep clock's less in the first catnap: SLEEP_COUNTER’ - 2 + SLEEP_COUNTER
RTCK 4) Time to wake up (t7):
In the last catnap, as the WU TIME is counting down, the following computations are done:

a) If (first catnap): If subscriber station is required to wake-up after the first catnap (see 3. g). the control does not get to 3. b where an adjustment is made for TA- SO the time x’ is accounted for in the residual ticks as: RTCK b) The CHIPX8_ SLEEP TIME is loaded with RTCK in (chips) and counted down at chipxS, to eventually wake up the subscriber station.
5) Re-acquisition upon wake up (too):
a) The preceding calibration process ensures that the subscriber
station sleeps for an integer number of FN rolls with very high
accuracy (depends on the drift estimation). Consequently, the
searcher should find the pilot with minimal offset relative to its
position before sleep. Any error in the drift compensation shows
up as "re-acquisition slew'b) The re-acquisition slew is stored to be used later in the next
sleep cycle to run the feedback loop to modify or correct the
DDC as will be shown in the next section.
As noted above, the FEE is initially used to estimate the manufacturer specific sleep crystal's frequency F’’- from which the
nominal frequency F’:’ derived. After the initial frequency estimation, if the
subscriber station goes to the access/traffic channels/AMPS system, its internal temperature could increase considerably resulting in the dynamic
frequency F’’’ to differ from its initial estimate. To handle this situation,
the FEE is used to estimate the dynamic frequency drift every time the unit returns to the slotted-paging mode.

However, this 'one time'‘ estimation of the dynamic drift at the beginning of slotted mode is not typically sufficient since the change in the frequency may occur over several sleep cycles as the unit cools off to its ambient temperature. Furthermore, changes in ambient temperature occur as well.
It can be shown that a given error made in the drift compensation of
the calibration results in a proportional pilot-drift (or re-acquisition slew) on
wake up. For example, if the subscriber station has to sleep for and a
calibration error resulted in only worth of sleep, the searcher will
see the pilot drift by upon wake up. This fact is utilized in setting up a feedback loop that adaptively modifies the dynamic drift compensation (DDC) to minimize any error.
FIG. 5 is a functional block diagram of the feedback loop. The calibration process described above is performed by a sleep calibration unit 200, which accepts the following four external inputs:
1. Slow crystal's dynamic frequency F!.’. , which is to be tracked,
2. Nominal slow clock frequency F!’. , a constant after the power-up
estimation,
3. Fixed drift compensation Ni-oc- a constant after power-up
estimation, and
4. Dynamic drift compensation NODC. which is the tracking variable.
The sleep calibration unit employs these values in the sleep
calculation equations described above to determine when the wake
up other components of the mobile station for receiving paging
signals or for handling other required tasks. As part of the sleep

calculations, the sleep calibration unit counts cycles of the slow sleep clock during sleep periods. The sleep cerebration unit eventually outputs a wake up signal that is used by other components of the mobile station.
The sleep calibration unit is employed with a feedback loop provided to compensate for drift in the slow clock crystal frequency so that the wake up signal is issued in synchronization with paging signals issued by the base station to minimize pilot reacquisition time. Hence, the aim of the feedback mechanism is to use F’’,
NFDC NDDC to derive an adjusted value for NDDC (used in the sleep calculations described above) to compensate for changes in the slow crystal frequency F’f..
FIG. 5 also shows a conceptual flip-switch (FS) 202 that determines the source of NDDC- Very time the subscriber station leaves the slotted-paging mode (due to reasons detailed above) the switch is set to position 'A\ Consequently, the FEE supplies the initial estimate of the dynamic drift once the station comes back to the slotted-paging mode. After thus initializing the loop, the switch is moved to position 'B' and stays there as long as the unit is in slotted-paging mode. While in position B, a loop filter 204 supplies a corrected estimate of NDDC-
At each paging slot, the mobile station performs a pilot re-acquisition process to reacquire the pilot signal from the nearest base station. Once the pilot is reacquired, a precise timing value is received from the base station representative of the true time. As noted above, any offset between the timing values provided by the

base station ad timing values as detennined within the mobile station is slew. The amount of slew is detemnined based upon a comparison of the respective timing signals of the mobile station and the base station. The slew is evaluated as a slew per PN roll. A signal representative of the slew per PN roll is applied to the feedback loop filter every sleep cycle. The loop filter calculates an adjusted value for the NDDC based upon the value of the slew/PN roll and from predetermined loop values described below. The adjusted value of NDDC is then applied to the SLEEP COUNTER as described above in section 3.d to compensate for any drift in the sleep mode clock. Note that the value for NDDC is not applied directly to the loop filter. Rather, only the current value of the slew is applied. Nevertheless, with proper selection of the predetermined values used in the loop filter, the filter outputs an adjusted value of NDDC- The adjusted value is determined by the loop filter so that the amount of slew in the next pilot reacquisition cycle should be less than before. With repeated iterations, NDDC converges on a substantially fixed numeric value having a value sized to ensure that the slew is near zero. Iterative reduction of the slew to near zero typically occurs very quickly following the re-entry of the mobile station into the slotted-paging mode. Thereafter, the feedback loop provides any slight adjustments to NDDC to maintain the slew near zero. In this manner, the wake up signal output by the sleep calibration unit remains substantially in synch with paging slots of the base station so that pilot reacquisition time is minimized.

The appropriate values for use in the feedback loop to reduce the slew to near zero and to maintain it near zero depend upon the particular characteristics of the mobile station, the sleep clock and the overall wireless system and are determined, for each particular embodiment, via routine experiments or other conventional techniques. Also, the choice of the order of the loop filter is dependent on the type of input frequency transient that needs to be tracked. If the slow crystal only has a constant frequency uncertainty, a first order loop is sufficient to track the constant frequency offset. However, in practice the frequency transient has a parabolic shape which makes a second or third order loop filter more desirable. For small slot-cycle-indices most often used in practice (SCI=0,1,2), the frequency transient is approximated very well by a simple ramp function, which is tracked wide minimal steady state error by a second order loop.
If the loop is iterated every sleep with the slew S
where B’ and (‘ can be chosen according to the input signal and noise characteristics. The "noise" in the loop arises due to the fluctuations in the pilot position in a multi-path and fading environment.
The expressions for the sampled loop gains given in Eq. 5 are valid under the assumption that the loop is uniformly sampled, i. e., if and only if

the loop iteration interval TSLEEP remains constant. For a given SCI, the sleep duration can be expressed as: TSLEEP =2' x 1.28 -TACTIVE. where TACTIVE is the time spent by subscriber station demodulating the paging channel when it is awake. Since Tanker depends on the length of the paging channel messages, there is no guarantee for some implementations that TSLEEP is a constant. Consequently, for those implementations, because the loop is non-uniformly up dated in time, the continuous time feedback loop approximation to a sampled loop that gave rise to Eq. 9 may require adjustment.
Although the sleep cycle duration varies randomly varying, it is at substantially least guaranteed to be a multiple of PN roll. This fact is exploited to formulate a loop configuration with a frequency error defined as slew/PN roll (S
The loop gains so computed for a single PN roll sleep cycles can be used for other sleep lengths TSLEEP while keeping in mind that the effective loop noise band-width is no longer Bj and is dependent on the SCL

The exemplary embodiments have been primarily described with reference to block diagrams and flow charts illustrating pertinent features of the embodiments. As the flow charts, each step therein represents both a method step and an apparatus element for implementing the method step. The apparatus element may represent a means for implementing the method step, an apparatus for implementing the method step or other structural element for implementing the method step. It should be appreciated that not all components of a complete implementation of a practical system are necessarily illustrated or described in detail. Rather, only those components necessary for a thorough understanding of the invention have been illustrated and described. Actual implementations may contain more components or, depending upon the implementation, fewer components. The description of the exemplary embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art and the generic principles defined herein may be applied to other embodiments without the use of the inventive faculty. Thus, the invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

WE CLAIM:
1. A method for compensating for frequency drift within a sleep clock signal used during a slotted paging mode of operation of a wireless mobile station, said mobile station in periodic communication with a base station providing timing signals, said method comprising the steps of: determining an initial frequency of the sleep clock signal following power-up of the mobile station; determining a fixed frequency drift compensation factor representative of a difference between the initial frequency of the sleep clock signal and a pre-determined nominal frequency ; estimating a dynamic frequency error compensation factor representative of a difference between the initial frequency and a current frequency of the sleep clock signal; and iteratively updating the dynamic frequency error compensation factor during the slotted mode of operation by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew.
2. The method as claimed in claim 1 wherein the step of determining the nominal frequency of the sleep clock signal is performed once following each power up of the mobile station.
3. The method as claimed in claim 1 wherein the step of estimating the dynamic frequency compensation factor is performed once for each entry into the slotted mode of operation.

4. The method as claimed in claim 1 wherein the step of determining a new
value for the dynamic frequency compensation factor is performed once
each cycle of the sleep clock signal.
5. The method as claimed in claim 1 wherein the feedback loop
includes a loop filter represented by:

wherein BL is a predetermined loop noise bandwidth value, ^ is a predetermined damping ratio and wherein a length of the sleep period is a multiple of The which is a predetermined time period.
7. The method as claimed in claim 1 wherein the order of the loop filter
is selected based upon a degree of uncertainty in the frequency of the sleep
clock signal.
8. The method as claimed in claim 7 wherein the frequency of the sleep
clock signal is constant and wherein a first order loop in employed.

9. The method as claimed in claim 7 wherein an uncertainty in the sleep clock signal is represented by a parabolic function and wherein the loop is at least a second order loop.
10. The method as claimed in claim 1 wherein the wireless mobile station is configured to operate in both the slotted paging mode and within an AMPS mode and wherein a frequency error estimation circuit is employed to estimate a new value for the dynamic frequency error compensation factor subsequent to each transition from the AMPS mode to the slotted paging mode.
11. The method as claimed in claim 1 wherein the slew is determined by
periodically receiving timing signals from the base station and comparing
the timing signal from the base station with timing signal generated within
the mobile station.
12. A device for compensating for frequency drift within a sleep clock
signal used during a slotted paging mode of operation of a wireless mobile
station, said mobile station in periodic communication with a base station
providing timing signals, said device comprising: means for determining an
initial frequency of the sleep clock signal following power-up of the mobile
station; means for determining a fixed frequency drift compensation factor
representative of a difference between the initial frequency of the sleep
clock signal and a pre-determined nominal frequency; means for estimating
a dynamic frequency error compensation factor representative of a
difference between the initial frequency and a current frequency of the sleep
clock signal; and means, operative during the slotted mode of operation, for

iteratively updating the dynamic frequency error compensation factor by determining an amount of timing slew between the mobile station and the base station, and then determining new values for the dynamic frequency compensation factor by applying a value representative of the amount of the slew to a feedback loop configured to provide a new dynamic frequency error compensation factor having a value selected to achieve a subsequent reduction in slew.
13. The device as claimed in claim 12 wherein the means for
determining the nominal frequency of the sleep clock signal operates once
following each power-up of the mobile station.
14. The device as claimed in claim 12 wherein the means for estimating
the dynamic frequency compensation factor operates once for each entry
into the slotted mode of operation.
15. The device as claimed in claim 12 wherein the means for
determining an amount of slew in the sleep clock signal and for then
determining a new value for the dynamic frequency compensation factor
operates once each cycle of the sleep clock signal.
16. The device as claimed in claim 12 wherein the loop filter is
represented by:

17. The device as claimed in claim 12 wherein the loop filter is
represented by:

wherein B^ is a predetermined loop noise bandwidth value, is a predetermined damping ratio and wherein a length of the sleep period is a multiple of TpN which is a predetermined time period.
18. A device for compensating for frequency drift within a sleep clock
signal used during a slotted paging mode of operation of a wireless mobile
station, said mobile station in periodic communication with a base station
providing timing signals, said device comprising: an initial frequency
determination unit; a fixed frequency drift compensation factor
determination unit; a dynamic frequency error compensation factor
determination unit; and a feed back unit, operative during the slotted mode
of operation, for iteratively updating the dynamic frequency error
compensation factor by determining an amount of timing slew between the
mobile station and the base station, and then determining new values for the
dynamic frequency compensation factor by applying a value representative
of the amount of the slew to a feedback loop configured to provide a new
dynamic frequency error compensation factor having a value selected to
achieve a subsequent reduction in slew.

Documents:

1644-CHENP-2007 AMENDED CLAIMS 18-09-2013.pdf

1644-CHENP-2007 CORRESPONDENCE OTHERS 18-09-2013.pdf

1644-CHENP-2007 AMENDED PAGES OF SPECIFICATION 03-09-2013.pdf

1644-CHENP-2007 AMENDED CLAIMS 03-09-2013.pdf

1644-CHENP-2007 CORRESPONDENCE OTHERS 25-04-2013.pdf

1644-CHENP-2007 FORM-3 03-09-2013.pdf

1644-CHENP-2007 OTHER PATENT DOCUMENT 03-09-2013.pdf

1644-CHENP-2007 OTHERS 03-09-2013.pdf

1644-CHENP-2007 POWER OF ATTORNEY 03-09-2013.pdf

1644-CHENP-2007 CORRESPONDENCE OTHERS 18-01-2012.pdf

1644-CHENP-2007 EXAMINATION REPORT REPLY RECEIVED 03-09-2013.pdf

1644-chenp-2007-abstract.pdf

1644-chenp-2007-claims.pdf

1644-chenp-2007-correspondnece-others.pdf

1644-chenp-2007-description(complete).pdf

1644-chenp-2007-drawings.pdf

1644-chenp-2007-form 1.pdf

1644-chenp-2007-form 26.pdf

1644-chenp-2007-form 3.pdf

1644-chenp-2007-form 5.pdf

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Patent Number

257541

Indian Patent Application Number

1644/CHENP/2007

PG Journal Number

42/2013

Publication Date

18-Oct-2013

Grant Date

14-Oct-2013

Date of Filing

20-Apr-2007

Name of Patentee

QUALCOMM INCORPORATED

Applicant Address

5775 MOREHOUSE DRIVE, SAN DIEGO, CALIFORNIA 92121-1714, USA

Inventors:

#	Inventor's Name	Inventor's Address
1	CHALLA, RAGHU	9494 CARROL CANYON ROAD, #61 SAN DIEGO, CA 92126, USA
2	BARGHOUTI, IHAB	3899 NOBEL DRIVE, #1214 SAN DIEGO, CA 92122, USA

PCT International Classification Number

H04B

PCT International Application Number

PCT/US2000/033263

PCT International Filing date

2000-12-07

PCT Conventions:

#	PCT Application Number	Date of Convention	Priority Country
1	na	1900-01-01	IB