Title of Invention  A METHOD AND SYSTEM OF SOLID ANGLE CROSSTALK CANCELLATION FOR BEAMFORMING ARRAYS 

Abstract  A system for improving an output of a transducer signal comprising: at least one transducer; a beamformer; at least one chosen, fixed input beam; an algorithmic block adapted for producing a desired resulting output beam having a narrowed onaxis beamwidth, wherein the narrowed onaxis beamwidth of the desired resulting output beam is produced by superpositioning a desired main beam with a beam steered at an angle from the axis of the desired main beam; and an output signal comprising the desired resulting output beam having a narrowed beamwidth. 
Full Text  FORM 2 THE PATENT ACT 1970 (39 OF 1970) & The Patents Rules, 2003 PROVISIONAL/COMPLETE SPECIFICTION (See section 10 and rule 13) 1. TITLE OF THE INVENTION "A Method and System of Solid Angle CrossTalk Cancellation for Beamforming Arrays." 2. APPLICANT (a) NAME : Shure Incorporated (b) NATIONALITY: A company incorporated under the laws of United States of America (c) ADDRESS: 222 Hartrey Avenue, Evanston, Illinois 60602 (US) 3. PREAMBLE TO THE DESCRIPTION COMPLETE The following specification particularly describes the invention and the manner in which it is to be performed. A METHOD AND SYSTEM OF SOLID ANGLE CROSS TALK CANCELLATION FOR BEAMFORM1NG ARRAYS. CROSSREFERENCE TO RELATED APPLIC ATIONS This application claims priority to U.S. Provisional Application, Serial No. 60/276,371, filed March 16, 2001, and U.S. NonProvisional Application filed on February 27, 2002 for which a serial number is not yet available, bom entitled "Solid Angle CrossTalk Cancellation for Beamforrning Arrays". BACKGROUND OF THE INVENTION This invention relates to microphones, in particular, interference cancellation of a signal received by a microphone, and, more particularly, to techniques for canceling the solid angle crosstalk of a signal and narrowing the width of a beampattem by subtracting off signals coming from a region of space shared by said beampattem and single or multiple overlapping beampattern(s). In acoustic (audio) signal processing, a signal can be subtracted from another signal by combining the two signals, also known as superpositioning. More precisely, cancellation of any signal may be achieved via linear superposition of an inverted exact duplicate of the signal with itself, or with a second signal which is highly correlated with the exact inverse of said signal. For example, a signal is typically a sinusoidal wave with a peak and a trough representing a positive and negative displacement, respectively, from a mean of the signal wave. When said second signal is combined vrith me first signal, the displacement of the two signals is summed at each point along the intersection of the two signals or waves. When a positive displacement is summed with a negative displacement at a particular point, the resulting combined wave at that point is the difference in the two displacements. When two positive displacements are summed, the resulting combined wave at that point is the sum of the displacements. A transducer converts an acoustic signal to an analog electrical signal. Though referred to simply as "signals" for convenience, acoustic signals are specifically continuous voltage (analog) conversions of atmospheric compression and expansion about static mean pressure via physical coupling of the transducer to the medium. For acoustic applications said transducer is a microphone, hydrophone, geophone, or similar device. Digital signals are the conversion of said analog signals to numerical data by an analogtodigital converter (ADC). United States Patent No. 6,049,607, to Marash, et al., ('607) is incorporated herein by reference. The '607 reference describes a system used to cancel a signal, particularly an echo or multipath. In one embodiment, '607 uses a linear or arbitrary distribution of receivers. In this embodiment, '607 cancels an echo by recognizing a signal received by a plurality of microphones with time delay steering, for example, and comparing that signal to a second channel carrying an incoming signal. The system thus recognizes the signal at the second microphone to be farfield echo, and subtracts the signal from the total signal received by the plurality of microphones via superpositioning. The method of superpositioning is implemented via selection of one or more input beamformers, and bandlimited adaptive filters. Such a system is continuously adaptive. More specifically, '607 uses continuously adaptive, digital signal processing (DSP) on a' number of steered beams to subtract signal from a person on the other end of a transmission line from the voice of the talker (target signal) received by an array in the transmission room. It does this by running a number of bandlimited adaptive filters on a plurality of beams, and subtracting the output signals from the "target" signal. This can result in a "pumping" of background noise as the filters continuously "look" for signals to cancel (i.e. continuously adapt)  as long as threshold conditions are met Tumping," as used herein, refers to a situation where the output is not constant, and, accordingly, the background output is changing. This allows crossover leak from multiple signals, echoes, as well as rapid changes in signal characteristics, th the following discussion the term "noise" refers to any signal that is not considered to be desirable output The filtering in '607, simply stated, is performed by spUtting the signals from multiple beams into the bandlimited frequency domains and not passing those bandlimited signals that are considered undesirable. The '607 process is adaptive according to signal received and continually must recalculate the steering based on the signals received. The '607 process splits the signal of multiple beams into bandlimited frequency domains and adaptively filters each domain before recombining each at the output This causes the quality of the output signal to vary continuously. A microphone system incorporates the method of United States Patent Nos. 5,825,898, to Marash, et al., ('898) and 6,084,973, to Creen et. al., ('973), which are each incorporated by reference herein. The signal received by the group of microphones is split into multiple signals of fixed frequency bandwidth, and the multiple signals are analyzed for undesirable/interfering signals. The bandlimited beams are steered about the axis of a reference beam or microphone and subtracted from the reference beam or microphone. "Steering a beam," as used herein, is a term used to describe rotating the beam around a reference point on a polar graphical representation of the signal. As used herein, the term "adaptive" refers to the fact that the system continually monitors the input signals and removes what are considered undesirable/interfering signals, continually adjusts the steering of the beams, and continually adjusts portions that are overlapped for subtraction via filtering. This is known in the field of the art as "null steering," or, because it includes bandlimited adaptive filtering, "bandlimited null steering." The '898 and '973 references are based on principles originating in telecommunications applications, such as speech directed at a handsfree telephone, that have been applied to highend audio systems. Accordingly, it is ideally suited and reasonably functions only for a narrow band of signal range (bandwidth). Therefore, over a broad band, '898 has problems, particularly with processing full range of acoustic signals for high quality sound reception, processing, and amplication. Accordingly, the methods taught by the '898 and '973 references have a number of problems. The methods of '898 and '973 are confused by additional and/or complex (variable state) signals. Signals arriving on the main axis are desirable, and signals arriving from off the main axis are considered undesirable. Bandlimited cancellation beams are steered to angles on a continually adaptive (frequency and time dependent basis). The methods can experience distinct problems analyzing reflections because the time delay for an echo may be great enough that the system may no longer view it as an echo but instead as a new signal. Multipath acoustic signals can also cause problems for the signal processing. The direction of the steering will be constantly changing with respect to frequency as multiple beams are steered in multiple directions. As the system must isolate and maintain ever changing cancellation or "null steering" beams, beams may disappear and reappear based upon the changing of the audio source, the processing possible by a microphone system utilizing these methods is dependent on the number of simultaneous adaptive beams that the system hardware can support. The resulting directivity partem of the microphone, as a function of frequency, is therefore not constant and is forever changing. Additionally, the background noise can be pumped if not cancelled properly. Pumping, in simple terms, is the rapid variation of output signal caused by continually adaptive switching between pickup patterns directed at different solid angles and therefore containing various spectral content (differing frequency signatures) over time. If the superpositioned noise signal is not the inversion of or a high correlation to the undesired signal, such as simply being not properly aligned in time (phase) or another misapplication, the superpositioned signal increases the total combined uncorrelated signal (noise) instead of causing the undesired signal to tend toward zero amplitude (thereby reducing ratio of desired signal to noise). This is called pumping due to the rapid variation in the spectral content of the output signal based on the superposition of beamformers or nulls, which changes on a contmually adaptive basis. Additionally, by implementing bandlimited null steering, the overall shape of the total pickup pattern of the transducer array as a whole will continuously change. This may result in highly inconsistent pickup patterns across the set of frequency bands. Offaxis signals (noise, undesirable signals) • pump up and down, causing rising and lowering levels of noises as the beampattems and output spectra of their associated signals contmually adapt Simply stated, there are a number of problems known in the art that result from using a continuously adaptive signal processing method. As a result of these problems with the methods and apparati disclosed by these U.S. Patents, Nos. 6,049,607 *607, 6,084,973, and 5,825,898, continuously adaptive microphone pickup algorithms are not appropriate for complex signals associated with high quality audio applications, especially in enclosed environments, because, for instance, they may present multiple signal paths to the transducers), such as sound reflections, resulting in continuously variable signal output. Beamforming is known and practiced in various manners. It is possible, and most typical, to form beams in a system requiring multiple transducers or transducer elements. However, it is possible to utilize a single transducer, as is described in United States Patent No. 5,862,240, to Ohkubo, et al. Okhubo is directed towards a system for utilizing multiple sound paths to a single microphone or transducer element, and its specification is incorporated herein by reference. Further, it is known in the art that multiple tubes in conjunction with insulation and varying lengths may be used to attenuate and phase shifted sound in multiple tubes for beamforming and steering purposes. In addition, other arrangements for forming beams are disclosed by U.S. Patent No. 5,651,074 to Baumhauer, et al., and U.S. Patent No. 5,848,172 to Allen, et al., the specifications of which are incorporated herein by reference. BRIEF SUMMARY OF THE INVENTION  The applicant has concluded through an improved understanding of spatial filtering and acoustic signal processing that a better method for improving onaxis pickup is simply to eliminate offaxis pickup by inverse superposition of properly scaled signals from one or more pickup patterns which share overlapping solid angles or regions of space with one or more main '■ (desired) pickup patterns. Additionally, applicant has concluded that the method of the disclosed reference patents, or similar methods which result in continuous changes of the pickup partem of the receivers), introduces detrimental additional random signals by continuously pumping varying lobes of an adaptive noise cancellation algorithm. m accordance with one aspect of the present invention, generally stated, the method "'processes nonadaptive beams in a parallel manner. A microphone receives a combined signal recognizable in a polar plot as lobes or beams. The method processes beams to either side of desired, or main, lobes or beams. The method recognizes multiple lobes which overlap either in two dimensions or in three of a polar plot A weighted cancellation beam is a signal derived directly from a beam steered to an angle by phase or time delays, causing an overlap between the >£ cancellation beam and the desired beam(s). The superpositioning of these weighted cancellation beams with the desired beams results in the removal, or cancellation (more appropriately, reduction), of the edges of the profile of the desired beams or lobes. Further, in accordance with the present invention, a user of the system may have a particular direction from which a signal is expected. Accordingly, the desired beampattern can be steered in the desired direction, and the edges of the profile of the beam signal received from the desired direction can be removed in this manner, thereby attenuating the signal and removing undesired interference or background signal. The present invention utilizes beamforming. Beamforming is known in the art in various manners and implementations. The present invention can utilize beamforming accomplished by 0£ digital, analog, or acoustic pathlength delay beamforming. BRIEF DESCRIPTION OF THE DRAWINGS In the drawings, Fig. 1 is a schematic view of the present invention; Fig. 2 is a representational view of an idealized polar plot of a beam of the present invention with its central axis at zero degrees; Fig. 3 is a representational view of an idealized polar plot of a beam of the present invention with its central axis steered from zero degrees by angle 0; Fig. 4 is a polar plot of the output of signals processed and unprocessed by the present invention; Fig. 5 is a polar plot of various frequencies signals unprocessed by the present invention; Fig. 6 is a polar plot of various frequencies signals processed by the present invention; Fig. 7 is a polar plot of various frequencies signals unprocessed by the present invention; Fig. 8 is a polar plot of various frequencies signals processed by the present invention; 3 DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT m This invention uses additional, overlapping nonadaptive beams to narrow the beamwidth of an existing beamformer without attempting to cancel a specific interfering source or cancel signals strictly on a bandlimited basis. Beamforming refers to the process or reinforcement of an acoustic signal from a specific angle by the coherent superposition or "stacking" of a plurality of elemental signals which have been phase delayed or time delayed to timealign the acoustic 'i emissions originating from that angle. Herein, "beampattern" refers to the magnitude of the sensitivity of one or more transducers to acoustic signals as a function of aznnuthal angle. This is commonly referred to in the art as the directivity function. In a particular direction of a recognizable lobe of a signal beam, the signal from the edges of the lobe, represented as left and right sections of the lobe in a polar plot, is considered to be interference because it comes from a segment of space that does not contain the source of interest As an attempt to identify the edges of the lobes is not made, it is of no consequence whether the signal is periodic or aperiodic. The invention isolates the offaxis signals and uses linear superpositioning. As used herein, crosstalk cancellation is used to denote the process of phase or delay steering a cancellation beam from a main beam such that a region of beampattem overlap exists, superpositioning the inverted and/or attenuated signal of the cancellation beam with the main beam, and producing a resulting desired narrower beamwidth for the main beam. Referring now to the drawings. Fig. 1 represents a system 10 of the present invention which processes input signals I and produces output signal O. Inputs I may be multiple input signals received by a single transducer T, or microphone, or by a plurality of transducers T. As is known in the field of the art, a microphone is principally a transducer that converts an acoustic audio signal into an electrical audio signal. However, a single microphone can contain multiple transducers, as well as a single transducer can receive multiple acoustic signals that are separable as distinct. The input signals I are analog signals derived from acoustic sources (not shown) located away from the transducers T. Once converted to analog electrical signals, the input signals I are converted from analog to digital data, represented by analog to digital converters 12. The A/D converter 12 sends the digital signals D to a Phase/Delay or beamformer 14. The signals D are then converted to a set of signals which are postprocessed by postprocessing blocks/filters 16 to produce output beamformer signals B1, B2 BN. The process of receiving acoustic signals (input signals) I by transducers T and converting these to digital signals D that have been filtered and summed is known in the field of the art. This process can be accomplished by a dedicated microprocessor, or by a microprocessor or computer machine performing computer executable instructions carried as software, or by any other means of processing these steps (i.e. analog circuitry). Next, crosstalk cancellation of the present invention is performed, represented by an algorithmic block 20. The block 20 includes amplifiers/weighting coefficients and an algorithm. Means for the algorithm may be analog electronics, may be a microprocessor, or a computer performing executable instructions, or any other means for performing these steps, as are known in the art. The coefficients may be preprogrammed or carry onboard instructions, as well as are controlled by the algorithm. The processing that occurs in the system 10 incorporates a number N of output beams, represented as Bi, B2 BN, collectively referred to as BN. As each output beam BN may provide a component of noise in a particular desired signal, it is provided that each output beam BN may provide a portion of signal to be removed via superpositioning from the desired signal. In order to weight each portion of signal from each output beam BN2, an attenuation coefficient aN is provided (typically on the order of 0.00 to 0.20, though not necessarily) for output beams 1 to N. The beams can be denoted as Bx for desired beams from 1 to X. The beam Bx follows the equation Bx = £ aNBN. This equation is a summation that occurs in block 20. This crosstalk cancellation results in the desired lobes or beams as signals, represented by M in Fig. 2, which are then summed to produce me output signal Q. The output signal O follows the equation Q = ZBx In Fig. 1, the method of beamforming may be any method of beamforming, including delay/sum, and frequency domain beamforming. The optimal practice of the invention results from beamforming mat produces beams with predictable overlapping segments. In Fig. 2, an idealized twodimensional polar plot of signal received by N transducers is depicted. Along the horizontal axis of Fig. 2 are points representing multiple transducers T. As noted above, each transducer T may be a separate microphone, may be multiple transducers within a single microphone, or may be portions or elements of a transducer T that allows for identifying a distinct audio signal represented as a beam as in a polar representation, as shown in Figs. 13. The transducers T may be of any number (even or odd), and such are represented in the quantity of N. In addition to noting the transducers T need not necessarily be a separate and discreet microphone but may also be a point on a microphone where the microphone is capable of perceiving audio (acoustic) signals at a discreet location, it should also be noted that mis array of transducers T need not be linear in either spacing or overall shape. The central lobe is the main beam M and is the desired beam. On either side of the main beam M are two cancellation beams CL, CR. hi Fig. 2, the steering angle © of the main beam M is 0°, coinciding with the central axis of the main beam M. The central axes of the cancellation beams CL, CR are offset from the central axis of the main beam M by steering angles OL, $R> respectively, and $L and OR. The main beam M initially has a beamwidth p on a polar representation. The beamwidth p may or may not be known. The width of the main beam is generally known by either simulation or measurement. The widths of the cancellation beams may be determined by simulation or experiment. The resulting beamwidth is a function of the angle and amplitude coefficient of the cancellation beams  and therefore the amount of overlap. This may or may not be determined in advance by simulation or measurement. This may be determined by empirical measurement of the directivity pattern of the system. The beamwidth p is assumed to contain a desired signal accompanied by undesirable noise along its edges (here, all unwanted signals are considered noise). It is further assumed that the elimination of undesirable/interfering signals produces the resulting beam with a beamwidth P'. A desired resulting beamwidth p' may be calculated in advance by simulation methods or "dialed in" on real time hardware by adjusting the amplitudes of the cancellation beamformer signals (weighting of cancellation beam output signals). As discussed above, this invention is not continuously adaptive, as are prior art embodiments. A user of the system can "dialin" or adjust the coefficients and adjust the algorithm, or the algorithm can adjust the coefficients. During a setup process, the system can be, through trial and error, adjusted to an optimal state. As the characteristics of electronics can be particular to each component despite careful manufacturing, a small amount of adjustment is typically considered necessary for optimal operation. However, during operation, the setup of the system 10 is quasistatic, obviating the need for continuous calculations, recalculations, and calibrations during operation. A desired beam can be steered to a desired direction, and then the process of the present invention can be utilized. In other words, one must know the direction of the desired signals to be received by the system and the regions that are to be subtracted. Having a knowledge that an acoustic signal is to originate from a particular direction, one selects a steering angle © for the main beam M and specifies the regions to be removed to narrow the beamwidth p to the beamwidth P'. It should be noted that it is not necessary to have a specific target or sound source in order to steer a beam. Beamforming is accomplished by phasing (delaying) the signals from the array elements such that the resulting beam(s) steers in various directions. The existence of desired signals, or a target, is not a precondition for steering and narrowing a beam. Fig. 3 represents, by way of example, the main beam M at a steering (or steered) angle © other than 0°, in this case and by way of example © = 30°. Fig. 3 represents the instance where a known, desired acoustic source is located at 30° from the reference 0°. The methodology represented in Figs. 2 and 3 may be proved using Fourier analysis, including Fourier transform pairs, Fast Fourier transforms, or discrete, continuous, or fast (fast discrete) Fourier analysis. For instance, using twodimensional Fourier transforms, the main beam M has a beamwidth P, while a desired beamwidth is p'. The method uses spatial representations of signals to determine the required spatial filter for beamwidth p in order to produce beamwidth p'. The spatial representation, or spatial signal of P, is denoted as the function a(x, y). The spatial representation of p' is a'(x, y). Next, one denotes the function A(kx, ky) as the 2D Fast Fourier Transform (FFT) or wavenumber transform of a(x, y) while A'(kx, ky) is the wavenumber transform of the desired beampattern. As a direct analogy to 1D signal processing, there is a two dimensional (spatial) filter represented by the 2D Fourier transform pair H(kx, ky), h(kx, ky) where H(kx, ky) = A'(kx, ky) / A(kx, ky) in the wavenumber domain. The resulting required filter is the spatial representation denoted as the function h(x, y). The function h(x, y) is an inverse field representation and as such is referred to as a spatial filter for simplicity despite not operating as a filter is commonly known. A filter as is commonly known rejects me passing of certain portions of a one dimensional (time domain) signal. In simpler terms, the use of Fourier Transforms relies on some basic principles. In the case of a time domain signal, it is known that an input signal IE (not shown) can be used to produce a desired output signal array OE (not shown) with particular characteristics, in this case beamwidth, by applying an electronic filter FE (not shown). In the present system, the input signal IE is known and the desired output OE is known. Represented mathematically in the Time Domain, IBO)* FE(t) *= OE (t), where * represents the operator known as convolution. When the input signal IE and desired output OE are transformed, the equation represents me Frequency Domain, and reads as IE(O) X FE(CO) = OE(CO) where x represents the operator known as multiplication. This equation can then simply solved as FE(CB)  OE(G>) / IEO»), again, FE(OO) representing the filter in the Frequency Domain. Once the Frequency Domain filter has been determined, a reverse Fourier Transform on tile filter produces the filter in the time domain. For two dimensional (or spatial) signals, the signal is a function of distance in x and y dimensions, fe(x,y), and its transform is a function of wavenumber XgO^ky), for k=(2*pi*f)/c, where f is frequency and c is the propagation speed of the medium. This process is then implemented in the system 10. It should be recognized that, in the preferred embodiment, all processing and steering as discussed herein is done in the time domain, with fixed steering angles and fixed delay. Accordingly, in the preferred embodiment, Fourier analysis is used as a design tool and for 0£ proving the concept However, the scope of this application includes applications using the frequency domain as well. Li the frequency domain, Fourier analysis may be employed not only as a design tool and for proving the concept, but also as a production tool. Fourier analysis in the wavenumber domain requires a significant amount of computing power, and accordingly may not always be feasible considering overall system parameters. In the preferred embodiment, Fourier analysis, such as the 2D FFTs, is not performed by components of the system or any computer code. These calculations (the aforementioned "dialing in") are computed outside of the system 10, not only because of the potentially limited computing power but also because they involve computing the expected acoustic pickup pattern of the actual beamformer and a desired beamformer. The use of a 2D FFT may be applied as an outside design tool to precalculate/simulate expected beam patterns and determine proper cancellation beam steering and amplitude. For a time domain beamformer, fixed sampling rates result in fixed delays used for beamsteering, and therefore fixed steering angles. Accordingly, one can only predict beamwidths, angles, and overlap. Precise steering of the beams requires frequency domain beamfonning. The method chosen is based on the type of beamformer used (i.e., discrete delays or magnitude/phase filters). la the time domain, the method is simply steering cancellation beams to the left and/or right of the main beam such mat there is some overlap. At mat point the amplitudes of the cancellation beams may be adjusted until satisfactory results are achieved. This is typically the method one would choose when using discrete (fixed) delays for steering the beam (as in a digital, timedelay system), because the fixed delays dictate that steered beams can only occur at a limited number of fixed angles (for example, 20 degrees, 35 degrees, and 60 degrees). Precise steering of the beams requires frequency domain beamfonning. The use of a Fourier analysis validates the theoretical basis of the method, m the frequency domain, the method is applied to beams formed by discrete time delays, or frequency domain filters on a charmelbychannel basis. The second method comes from the above Fourier analysis. Since the two dimensional Fourier transform can be used to validate the time delay method amplitude "dialing in" of the cancellation beams, it may also be used to determine the steering angle of cancellation beams required, m the case where filters are used to steer the beamformers  rather man fixed time delays  precise phase delays can form cancellation beams that can be steered to almost any angle. Therefore the 2D FFT provides the angle, amplitude, and expected outcome in advance. Regardless of beamfonning method used, the beamwidth will vary for steered beams as the array aperture changes with the cosine of the steering angle. For the case of a time delay beamformer, in the time domain, there a limited number of steering angles. Provided the beam patterns overlap, the amplitude coefficients of the undesired beams may be "dialedin," or "tuned," to achieve satisfactory results. Therefore, one need not predetermine the beamwidths or precise steering angles, instead tuning the system to an empirically determined setting. Under either method, the process of validation used spatial (2D) Fourier transforms as a verification of experimental method and data. For instance, in a manner similar to solving for an inverse transfer function in the time domain, the spatial domain filter shows lobes pointed to approximately +/ 30 degrees as shown in figures 58. Given that the theoretical calculations verify and/or complement the experimental data, it is possible to use numerical representations of the actual and desired beampattems to solve for the magnitude and phase of a spatial filter, which will indicate the direction that cancellation beams should be steered to achieve the desired beampattern. This may be considered as part of the design process, particularly for frequency domain beamformers, but it is not necessarily part of the processing algorithm used on a "realtime" basis in the system 10. This process of wavenumber processmg with frequency domain beamforming could also be used with a feedback mechanism to control, or automatically "dialin," beam width adjustments. However, this requires processing power of a significant amount and is often not practical commercially. In both time domain and frequency domain beamformers, a beam can be chosen, but not an angle. In the practice of time domain beamformers with time domain phase delays, it is not possible to precisely steer a beam. When a sound source is present in a beam, that beam is used. Because the sampling rate is fixed, the delays are a function of the sampling period. This results in a number of fixed beams. In this case, it is simplest to adjust attenuation coefficients of the plurality of beams, which are steered to said fixed angles to the left or right of the desired beam(s). Twodimensional processing, such as discussed above, to set the coefficient values may be used, but is usually a formality. In the case of frequency domain beamformers, where beam steering is a function of the phase imparted to each signal, the use of two dimensional Fourier transforms would be necessary in order to determine both amplitude coefficients and steering angles of the cancellation beams. In addition, a target beam may be identified, and a steering angle may selected by adjusting the phase of the signal on each element using the describe Fourier transform filtering processes. Fig. 4 depicts a polar plot of two beampattems Si and S2 (signal sensitivity vs. angle). Beampattern Si is a 1kHz beampattern without crosstalk cancellation, while Sic denotes the same beampattern S\ with crosstalk cancellation. Beampattern S2 is a 3kHz beampattern without crosstalk cancellation, while S2c denotes the same beampattern S2 with crosstalk cancellation, AS can oe seen in rig. % uie pioi ui eacn beampattem Si and S2 has been narrowed. Because of the processing, there is a reduction of sensitivity to beampattem reception 1 at offaxis angles, reducing stray or undesirable signals (herein referred to as noise). This enhances the output by attenuating said offaxis signals. Figs. 58 represent polar plotted data for a variety of frequencies, both with and without crosstalk cancellation, tested in an anechoic chamber, each major division of the plot representing 10 decibels. Fig. 5 depicts signals without crosstalk cancellation at frequencies of 400, 600, 800, 1000,1200, 1600, 2000, 2400 Hz. Fig. 6 depicts the identical signals of Fig. 5 with crosstalk cancellation. Labeling each line as a particular frequency does not contribute to the understanding of the results of crosstalk cancellation. Accordingly, what should be noted about comparing Fig. 5 with Fig. 6 is that the lobed beams towards the center of the plot in Fig. 5 correspond to the same in the center of the plot in Fig. 6. In the lobed beams of Fig. 6, the spatial representations of the lobes are more defined and narrower. Similarly, the sidelobes (offaxis pickup lobes) of Fig. S have become smaller (narrower) in Fig. 6. Figs. 7 and 8 represent signals with frequencies of 2500, 2800, 3200,3600,4000, 4400, and 4700, without and with crosstalk cancellation, respectively. Similar to Figs. 5 and 6, Figs. 7 and 8 illustrate a narrowing and greater definition of the beam by utilizing crosstalk cancellation in accordance with the techniques of the present invention. Fig. 9 provides a flow chart of the method of the present invention. Input signal I is received by a transducer T which converts the acoustic audio signal into an analog electrical signal. An A/D converter 12 converts the analog electrical signal to a digital signal D. As represented in the present embodiment, the digital signal D is sent to the beamformer 14 and becomes an output beam 16. Block 18 provides the location or determines the location 0 (see Figs. 2, 3) for beam M. Blocks 14 and 18 produce a direction dependent signal sensitivity that can be represented in a graphical form as beams for a polar plot The signals, now viewed as beams, are passed to block 108 where the signals, if multiple signals are present, are summed. The summed beams are then sent to the block 20 represented as dashed lines. In further embodiments of present invention, it should be noted that any analog method for forming beams and applying nonadaptive cancellation using 2D FFT, other FFTs, or experimental (empirical) adjustment or tuning of the device maybe used. Additionally, it should be noted that, as a single microphone or transducer assembly can be used for multiple sound paths, and hence multiple acoustic signals (i.e. process signals from multiple simultaneous directional pickup patterns), a single microphone or transducer assembly may be implemented in the present application. An acoustic beamformer with multiple ports that can be used for forming independent beams may be utilized in the same manner as described herein. For example, the invention of U.S. Patent No. 5,862,240 to .Okhubo, et al., may be utilized as a single microphone or transducer element, and multiple tubes of various lengths in conjunction with insulation may be used to attenuate sound and create a phase shift in sound in multiple tubes. These methods and systems may then be used to form independent beams as is necessary for the present invention. The method and system of the present application may further use components that generally function with a similar result as a microphone. The method is equally applicable to arrays of similar transducers such as hydrophones and geophones. Though Fourier analysis is a principle means discussed in this application, it is clear that a number of mathematical computations could be supplemented for performing the mathematics, and the present methods are to be in no way limited to use of Fourier analysis. Such should be particularly clear as Fourier analysis may entirely be supplanted by empirical methods. It should be noted mat the steps in this invention need not be performed exactly as described. For instance, some of these steps may be performed by dedicated hardware, or circuitry, or by software applications, or by some combination of hardware, circuitry, and software. Accordingly, it is clear that the components of the system of the present invention may also be a one or a combination of hardware, circuitry, and software. For this reason, it is also clear that the invention is not necessarily dependent on the order or the location of steps or system components. As various changes could be made in the above constructions without departing from the scope of the invention, it is intended that all matter contained in the above description or shown in the accompanying drawings shall be interpreted as illustrative and not in a limiting sense. 

965mumnp2003cancelled pages(05012007).pdf
965mumnp2003claims(granted)(05012007).doc
965mumnp2003claims(granted)(05012007).pdf
965mumnp2003correspondence(11012007).pdf
965mumnp2003correspondence(ipo)(20032007).pdf
965mumnp2003drawing(05012007).pdf
965mumnp2003form 1(05012007).pdf
965mumnp2003form 18(07102005).pdf
965mumnp2003form 2(granted)(05012007).doc
965mumnp2003form 2(granted)(05012007).pdf
965mumnp2003form 3(05012007).pdf
965mumnp2003form 3(15102003).pdf
965mumnp2003form 5(05012007).pdf
965mumnp2003form 5(15102003).pdf
965mumnp2003formpctisa210(05012007).pdf
965mumnp2003power of attorney(05092003).pdf
965mumnp2003power of attorney(14102003).pdf
Patent Number  206481  

Indian Patent Application Number  965/MUMNP/2003  
PG Journal Number  30/2007  
Publication Date  27Jul2007  
Grant Date  27Apr2007  
Date of Filing  15Oct2003  
Name of Patentee  SHURE INCORPOTATED  
Applicant Address  222, HARTREY AVENUE, EVANSTON, ILLINOIS 60602, U.S.A.  
Inventors:


PCT International Classification Number  H04R 3/00  
PCT International Application Number  PCT/US02/07504  
PCT International Filing date  20020314  
PCT Conventions:
